RFID tag, interrogator and system with improved symbol encoding and decoding

ABSTRACT

An improved RFID Tag, Interrogator, and system wherein at least one tag modulates a radio frequency signal by modulated backscatter operations.

CROSS-REFERENCE TO RELATED APPLICATIONS

The present application claims priority from U.S. Provisional App. No.60/764,111, filed Feb. 1, 2006 and U.S. Provisional App. No. 60/804,368filed on Jun. 9, 2006, herein incorporated by reference in theirentireties.

BACKGROUND OF THE INVENTION

1. Field of the Invention

This invention relates broadly to wireless communication systems and,more particularly, to encoding and decoding of a backscatter radiofrequency signal in a radio frequency identification system.

2. State of the Art

Radio Frequency Identification (RFID) systems are used foridentification and/or tracking of equipment, inventory, or livingthings. RFID systems are radio communication systems that communicatebetween a radio transceiver, called an Interrogator, and a number ofinexpensive devices called Tags. The objectives of RFID systems are todesign a reliable and secure architecture, and to minimize the totalcost of the Interrogator and the Tags, while meeting the systemperformance requirements.

In RFID systems, the Interrogator communicates to the Tags usingmodulated radio signals, and the Tags respond with modulated radiosignals. For downlink communication from the Interrogator to a Tag, theInterrogator transmits a modulated radio signal that encodes theInterrogator's message. The Tag receives the modulated radio signal anddemodulates and decodes the Interrogator's message therefrom. For uplinkcommunication from a Tag to the Interrogator, the Interrogator transmitsa continuous-wave (CW) carrier signal. The CW carrier signal can be afrequency-hopping spread-spectrum (FHSS) carrier signal as is wellknown, thereby enhancing the system's ability to operate in a multipathenvironment. The Tag modulates the CW carrier signal using modulatedbackscattering operations whereby the antenna is electrically switchedfrom being an absorber of RF radiation to being a reflector of RFradiation, thereby encoding the Tag's information onto the CW carriersignal. The Interrogator receives the incoming modulated CW carriersignal and demodulates and decodes the Tag's information messagetherefrom. The uplink and downlink communication occurs in a half-duplexmanner such that a Tag will not perform communication while it iswaiting for communication from an Interrogator and also will notinterpret communication from the Interrogator while it is communicating.The Tag can be a passive-type tag that obtains its operating energy byrectifying the RF energy transmitted by the Interrogator and received atthe Tag's antenna. Alternatively, the Tag can be a semi-passive tag(sometimes referred to as semi-active tag) that is equipped with atleast one battery to provide operating energy to the Tag.

As described above, the Interrogator operates to receive the reflectedand modulated CW carrier signal and demodulate and decode the Taginformation message encoded therein. Typically, such functionality isaccomplished by homodyne detection wherein the received signal isamplified with a low noise amplifier whose output is mixed by aquadrature mixer that uses the same RF signal source as the transmitfunctionality. The in-phase (I) and quadrature (Q) components outputfrom the quadrature phase mixer are filtered and processed by a datarecovery circuit. The data recovery circuit can be realized in manydifferent ways including both analog, digital and hybrid analog/digitalimplementations. Typically, these implementations perform integrate anddump operations whereby the signal energy of the I component and/or Qcomponent is (are) accumulated during a symbol period. The accumulatedvalue(s) is (are) supplied to a symbol decision comparator that producesthe demodulated data stream. An example of such a receiverimplementation is described in U.S. Pat. No. 6,456,668 to MacLellan etal.

Disadvantageously, the integrate and dump methodology of the prior artreceiver designs has poor performance because it provides limitedknowledge of the energy of the signal as well as the noise process ofthe communication channel. These limitations reduce the signal to noiseratio of the receiver subsystem, which results in increased signal powerat the Tag (or decreased read range of the system) in order to maintaina prescribed bit error rate. The increased signal power at the Tag istypically realized by a larger Tag antenna, which increases the size andcosts of the Tag.

Therefore, there remains a need in the art for RFID Tags, Interrogatorsand systems that provide improved receiver performance (i.e., animproved signal to noise ratio) which allows for reduced signal power atthe Tag (or a larger read range of the system) while maintaining aprescribed bit error rate. Such improved receiver performanceadvantageously will not require an increase in the size and cost of theTag.

SUMMARY OF THE INVENTION

It is therefore an object of the invention to provide an RFID Tag,Interrogator, and system that provide improved receiver performance(i.e., an improved signal to noise ratio). Such improved performanceallows for reduced signal power at the Tag (or a larger read range ofthe system) while maintaining a prescribed bit error rate. The reductionof signal power at the Tag allows for smaller and less costly Tagdesigns while maintaining the prescribed bit error rate of the system.

It is another object of the invention to provide such an RFID Tag,Interrogator, and system that employ a form of biphase encoding foruplink communication from the Tag to the Interrogator.

It is a further object of the invention to provide such an RFID Tag,Interrogator, and system that employ a form of a modulated subcarrierencoding for uplink communication from the Tag to the Interrogator.

In accord with these objects, which will be discussed in detail below, aTag is provided for use in a radio frequency identification system. Aspart of uplink communication from the Tag to an Interrogator, the Taggenerates an uplink signal that represents a sequence of symbols. In afirst mode of operation, the uplink signal is generated in accordancewith a first signaling scheme wherein the uplink signal is derived bymultiplying a first-type bi-phase baseband waveform by a square wave.The first-type bi-phase baseband waveform has a phase inversion at leaston every symbol boundary and has a first symbol rate SR1, and the squarewave has a rate M*SR1, where M is selected from a number of differentinteger values. In a second mode of operation, the uplink signal isgenerated in accordance with a second signaling scheme wherein theuplink signal comprises a second-type bi-phase baseband waveform havinga phase inversion at least on every symbol boundary and having a secondsymbol rate SR2. The second symbol rate SR2 is different from the firstsymbol rate SR1. A modulator cooperates with at least one antennaeelement of the Tag to modulate a backscatter signal transmitted at theat least one antenna element in accordance with the uplink signal. Inthe preferred embodiment, the selection of the operational mode(including the selection of the integer value for M) is dictated bycommand data communicated to the tag as part of an RF signal received atthe least one antenna element.

The interrogator includes a transmitter that transmits the radiofrequency signal and a receiver that receives, demodulates and decodesthe modulated radio frequency signal in order to recover the uplinkmessage therein. The receiver operates in either a first or second modeof operation. In the first mode of operation, symbol decoding operationsare performed that decode a given symbol by generating a first set ofreference waveforms that are derived by multiplying first-type bi-phasebaseband waveforms by a square wave. The first-type bi-phase basebandwaveforms each have a phase inversion at least on every symbol boundaryand each have a first symbol rate SR1, and the square wave has a rateM*SR1, where M is selected from a number of different integer values. Ina second mode of operation, symbol decoding operations are performedthat decode a given symbol by generating a second set of referencewaveforms that comprise second-type bi-phase baseband waveforms eachhaving a phase inversion at least on every symbol boundary and eachhaving a second symbol rate SR2. The second symbol rate SR2 is differentfrom the first symbol rate SR1.

In the preferred embodiment, the symbol decoding operations of the firstmode process portions of a component of the modulated radio frequencysignal that are received over a first extended processing window. Thefirst extended processing window is significantly greater than the firstsymbol period dictated by the first symbol rate SR1. Most preferably,the first extended processing window has a time duration that is twotimes the first symbol period. Similarly, the symbol decoding operationsof the second mode process portions of a component of the modulatedradio frequency signal that are received over a second extendedprocessing window. The second extended processing window issignificantly greater than the second symbol period dictated by thesecond symbol rate SR2. Most preferably, the second extended processingwindow has a time duration that is two times the second symbol period.

It will be appreciated that such dual-mode Tag-to-Interrogator signalingprovides improved receiver performance (i.e., an improved signal tonoise ratio). Such improved performance allows for reduced signal powerat the Tag (or a larger read range of the system) while maintaining aprescribed bit error rate. The reduction of signal power at the Tagallows for smaller and less costly Tag designs while maintaining theprescribed bit error rate of the system.

According to one embodiment of the invention, the symbol decoderincludes multiplication means for samplewise multiplication of portionsof the component of the modulated radio frequency signal with portionsof the corresponding reference waveforms in the selected operationalmode; and accumulation means for accumulating results of themultiplication means over the extended processing windows in theselected operational mode. In digital implementations, the samplewisemultiplication may be realized by changing the sign of samples of themodulated radio frequency signal component in accordance with thereference waveform(s) portions.

According to another embodiment of the invention, the symbol decodingoperations employ multiple signal processing paths for carrying out oddsymbol processing in parallel with even symbol processing.

According to yet another embodiment of the invention, the symboldecoding operations employ signal processing paths that each employ arespective storage cell for storing the accumulation results from theprevious processing window. The stored accumulation results are added tothe accumulation results of the current processing window for carryingout symbol processing in the extended processing window of the selectedoperational mode.

Additional objects and advantages of the invention will become apparentto those skilled in the art upon reference to the detailed descriptiontaken in conjunction with the provided figures.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a functional block diagram of an RFID system in which thepresent invention can be embodied.

FIG. 2A is a pictorial illustration depicting amplitude shift keyingmodulation.

FIG. 2B is a pictorial illustration depicting phase shift keyingmodulation.

FIGS. 3A1 and 3A2 are pictorial illustrations of basis functions forgenerating an FM0 baseband waveform, which may be used forTag-to-Interrogator signaling in the RFID system of FIG. 1.

FIG. 3B is a state diagram that is used in conjunction with the basisfunctions of FIGS. 3A1 and 3A2 to generate an FM0 baseband waveform.

FIG. 3C is a pictorial illustration of the data-0 and data-1 symbols ofan FM0 baseband waveform.

FIG. 3D is a pictorial illustration of symbol sequences of FM0 basebandwaveforms.

FIGS. 4A1 and 4A2 are pictorial illustrations of basis functions forgenerating a Modified-Miller baseband waveform.

FIG. 4B is a state diagram that is used in conjunction with the basisfunctions of FIGS. 4A1 and 4A2 to generate a Modified-Miller basebandwaveform.

FIG. 4C is a functional block diagram that illustrates themultiplication of the Modified-Miller baseband waveform by a high ratesquare wave to generate a Modified-Miller subcarrier waveform, which maybe used for Tag-to-Interrogator signaling in the RFID system of FIG. 1.

FIG. 4D is a pictorial illustration of symbol sequences ofModified-Miller subcarrier waveforms.

FIG. 5A is a pictorial illustration of a preamble waveform that precedeseach Query command as part of Interrogator-to-Tag signaling in the RFIDsystem of FIG. 1.

FIG. 5B is a pictorial illustration of a frame-synch waveform thatprecedes other commands (e.g., Select, ACK, Read, Write, Kill) as partof Interrogator-to-Tag signaling in the RFID system of FIG. 1.

FIGS. 6A and 6B are pictorial illustrations of two different preamblewaveforms that precede one or more reply data fields as part ofTag-to-Interrogator signaling in the RFID system of FIG. 1 in thoseinstances where FM0-type Tag-to-Interrogator signaling is employed.

FIG. 6C is a pictorial illustration of an end-of-signaling waveform thatterminates FM0-type Tag-to-Interrogator signaling.

FIGS. 7A and 7B are pictorial illustrations of two different sets ofpreamble waveforms that precede one or more reply data fields as part ofTag-to-Interrogator signaling in the RFID system of FIG. 1 in thoseinstances where Modified-Miller-subcarrier-type Tag-to-Interrogatorsignaling is employed.

FIG. 7C is a pictorial illustration of an end-of-signaling waveform thatterminates Modified-Miller-subcarrier-type Tag-to-Interrogatorsignaling.

FIG. 8 is a functional block diagram of a digital implementation of thedata recovery circuit of FIG. 1 in those instances where FM0-typeTag-to-Interrogator signaling is employed.

FIG. 9A is a pictorial illustration of a composite S₀ referencewaveform, which is the composite of the S₀-odd reference waveform ofFIG. 9B and the S₀—even reference waveform of FIG. 9C.

FIG. 9B is a pictorial illustration of an S₀-odd reference waveform,which corresponds to the data=0 symbol of the FM0 signal format andwhich is used for decoding of odd symbols in the data recovery circuitof FIG. 8.

FIG. 9C is a pictorial illustration of an S₀—even reference waveform,which corresponds to the data=0 symbol of the FM0 signal format andwhich is used for decoding of even symbols in the data recovery circuitof FIG. 8.

FIG. 10A is a pictorial illustration of a composite S₁ referencewaveform, which is the composite of the S₁—odd reference waveform ofFIG. 10B and the S₁—even reference waveform of FIG. 10C.

FIG. 10B is a pictorial illustration of an S₁—odd reference waveform,which corresponds to the data=1 symbol of the FM0 signal format andwhich is used for decoding of odd symbols in the data recovery circuitof FIG. 8.

FIG. 10C is a pictorial illustration of an S₁—even reference waveform,which corresponds to the data=1 symbol of the FM0 signal format andwhich is used for decoding of even symbols in the data recovery circuitof FIG. 8.

FIGS. 11A to 11E are signal waveforms that describe the signalprocessing operations carried out by the data recovery circuit of FIG.8.

FIG. 12 illustrates an analog implementation of the data recoverycircuit of FIG. 8 with like numerals designating analog-forms of thesignal processing functionality shown therein.

FIG. 13 illustrates an alternate embodiment of the data recovery circuitof FIG. 1 in accordance with the present invention.

FIG. 14 is a functional block diagram of a digital implementation of thedata recovery circuit of FIG. 1 in those instances whereModified-Miller-subcarrier-type Tag-to-Interrogator signaling isemployed.

FIGS. 15A1 and 15A2 are pictorial illustrations of an S₀ basis waveformand an S₁ basis waveform, respectively.

FIG. 15B is a functional block diagram that illustrates themultiplication of the S₀ basis waveform and the S₁ basis waveform ofFIGS. 15A1 and 15A2 by a high rate square wave to derive correspondingS₀ and S₁ reference waveforms.

FIGS. 15C1 and 15C2 are pictorial illustrations of the S₀ and S₁reference waveforms, respectively, which are derived from multiplicationby a square wave having a rate that is two times the symbol rate of theS0 and S1 basis waveforms (e.g., M=2), and which can be used fordecoding symbols in the data recovery circuit of FIG. 14.

FIGS. 15D1 and 15D2 are pictorial illustrations of the S₀ and S₁reference waveforms, respectively, which are derived from multiplicationby a square wave having a rate that is four times the symbol rate of theS0 and S1 basis waveforms (e.g., M=4), and which can be used fordecoding symbols in the data recovery circuit of FIG. 14.

FIGS. 15E1 and 15E2 are pictorial illustrations of the S₀ and S₁reference waveforms, respectively, which are derived from multiplicationby a square wave having a rate that is eight times the symbol rate ofthe S0 and S1 basis waveforms (e.g., M=8), and which can be used fordecoding symbols in the data recovery circuit of FIG. 14.

FIGS. 16A1 to 16A5 are signal waveforms that describe the signalprocessing operations carried out by the data recovery circuit of FIG.14 for the particular symbol sequence {0,0,x}.

FIGS. 16B1 to 16B5 are signal waveforms that describe the signalprocessing operations carried out by the data recovery circuit of FIG.14 for the particular symbol sequence {1,0,x}.

FIGS. 16C1 to 16C5 are signal waveforms that describe the signalprocessing operations carried out by the data recovery circuit of FIG.14 for the particular symbol sequence {0,1,x}.

FIGS. 16D1 to 16D5 are signal waveforms that describe the signalprocessing operations carried out by the data recovery circuit of FIG.14 for the particular symbol sequence {1,1,x}.

FIG. 17 illustrates an analog implementation of the data recoverycircuit of FIG. 14 with like numerals designating analog-forms of thesignal processing functionality shown therein.

FIG. 18 illustrates an alternate embodiment of the data recovery circuitof FIG. 14 in accordance with the present invention.

FIG. 19 is a high-level functional block diagram of an RFID tag, whichcan be configured to use FM0-type or Modified-Miller-subcarrier-typetag-to-Interrogator signaling in accordance with the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

Turning now to FIG. 1, there is shown an RFID system 10 that embodiesthe present invention. The RFID system 10 includes an Interrogator 12that operates to read information from a Tag 14 affixed to a sensor,container, rack, pallet, or object (not shown). Typically, the Tag 14 ismoved across the reading field of the Interrogator 12, although the Tag14 may be stationary and the Interrogator 12 may be moving, or both maybe moving or stationary. The reading field is defined as that volume ofspace within which successful communications between the Interrogator 12and the Tag 14 can take place. While the Tag 14 is in the reading field,the Interrogator 12 and the Tag 14 must complete their informationexchange before the Tag 14 moves out of the reading field.

The Interrogator 12 includes a Processor 16 that typically interfaces toa host system 18 (e.g., a workstation or possibly a network interfacethat provides for communication to a remote system via a data network).The Processor 16 manages the communication interface between theInterrogator 12 and the Tag 14. The host system 18 interfaces with theProcessor 16 and directs the communication between the Interrogator 12and the Tag 14. In response to control commands supplied by the hostsystem 18, the Processor 16 generates commands (e.g., Select, Query,Read, Write, Kill) that are formatted and encoded within a DownlinkInformation Signal 20 to be sent to the Tag 14. Signal Source 22generates a continuous-wave RF carrier signal with a center frequencydesignated f_(c). Modulator 24 modulates the Downlink Information Signal20 onto the continuous-wave RF carrier signal, and the Transmitter 26sends this modulated RF signal via Antenna 28 to the Tag 14.

The Tag 14 includes an Antenna 51 (for example, a loop or patch antenna)that receives the modulated RF carrier signal. This signal isdemodulated to a baseband signal using a detector/modulator (not shown),which is typically realized by a single Schottky diode. The diode shouldbe appropriately biased with the proper current level in order to matchthe impedance of the diode and the Antenna 51 such that losses of theradio signal are minimized. The result of the diode detector isessentially a demodulation of the incoming signal directly to baseband.The binary levels of the baseband signal together with the relevanttiming information (e.g., the bit clock) are recovered from the basebandsignal to thereby reproduce the Downlink Information Signal 20. Thisinformation is typically supplied to a processor (not shown), which istypically realized by an inexpensive 4-bit or 8-bit microprocessor, thatprocesses the Downlink Information Signal 20 to recover the particularcommand therein. The microprocessor then performs certain operationsthat are dictated by the particular command and generates a replycorresponding thereto. For example, the microprocessor typicallyperforms memory access operations that retrieves identification data(e.g., EPC data) stored in persistent memory in response to a Readcommand, and adds the retrieved identification data to the reply. Thereply is formatted and encoded within an Uplink Information Signal 40 tobe sent from the Tag 14 back to the Interrogator 12. The Tag modulatesthe received CW carrier signal using modulated backscattering operationswhereby the antenna is electrically switched from being an absorber ofRF radiation to being a reflector of RF radiation. Such modulatedbackscatter operations modulate the Uplink Information Signal 40 ontothe received CW carrier signal. The Interrogator 14 receives theincoming modulated CW carrier signal via antenna 30, demodulates anddecodes the Uplink Information Signal 40 therefrom, extracts the Tag'sreply message from the Uplink Information Signal 40, and processes theTag's reply message in order to determine subsequent control operations,all as described in detail hereinafter

In the preferred embodiment, the downlink and certain uplinkcommunications between the Interrogator 12 and Tag 14 (including thephysical layer, data-coding methodology, command and response structure,and collision arbitration scheme) are carried out in accordance with astandardized air interface specification promulgated by EPCglobal Inc.entitled “Class-1 Generation 2 UHF RFID Protocol for Communications at860 MHz-960 MHz”, herein incorporated by reference in its entirety. Thisair interface specification is summarized and referred to below as theEPCglobal UHF protocol.

In accordance with the EPCglobal UHF protocol, downlink communicationfrom the Interrogator 12 to the Tag 14 is carried out by the RadioSignal Source 22 generating an RF carrier in the frequency range between860 MHz and 960 MHz. The Processor 16 and modulator 24 cooperate tomodulate the RF carrier in accordance with the Downlink InformationSignal 20 using one of three well-known amplitude modulation schemes(i.e., Double-Side-Band Amplitude Shift Keying (DSB-ASK),Single-Side-Band Amplitude Shift Keying (SSB-ASK), Phase-ReversalAmplitude Shift Keying (PR-ASK)). The Downlink Information Signal 20utilizes a pulse-interval encoding (PIE)) format. The Transmitter 26transmits the modulated RF carrier over the Antenna 28. The Tag 14 iscapable of receiving the modulated RF carrier and demodulating all threeamplitude modulation schemes and decoding the pulse-interval encodedwaveforms of the Downlink Information Signal 20. The Tag 14 is apassive-type tag that receives its operating energy from the modulatedRF carrier transmitted by the Interrogator 12. The Radio Signal Source22 may generate a frequency-hopping spread-spectrum (FHSS) carriersignal in order to enhance the system's ability to operate in amultipath environment. The Tag 14 stores a field-programmable 96-bitelectronic product code (EPC) along with other data (e.g., KILL andACCESS passwords, user-defined data).

Uplink communication from a Tag to the Interrogator is carried out bythe Radio Signal Source 22, Modulator 24 and Transmitter 26 cooperatingto transmit via the Antenna 28 a continuous-wave RF carrier in thefrequency range between 860 MHz and 960 MHz. The CW carrier signal canbe a frequency-hopping spread-spectrum (FHSS) carrier signal as is wellknown, thereby enhancing the system's ability to operate in a multipathenvironment. As previously mentioned, the Tag 14 modulates the CWcarrier signal using modulated backscattering operations whereby theantenna is electrically switched from being an absorber of RF radiationto being a reflector of RF radiation, which modulates the Tag's UplinkInformation Signal 40 onto the CW carrier signal.

The modulated backscattering operations employ either amplitude shiftkeying (ASK) modulation or phase shift keying (PSK) modulation. ASKmodulation is a modulation technique whereby the CW carrier signal ismultiplied by a digital signal f(t) as shown in FIG. 2A. Mathematically,the modulated CW carrier signal s(t) is given by the followingexpression:s(t)=f(t)sin(2πf _(c) t+φ).PSK is modulation technique that alters the phase of the CW carriersignal. Mathematically, the modulated CW carrier signal s(t) is given bythe following expression:s(t)=sin(2πf _(c)+φ(t)).Binary phase-shift-keying (BPSK) utilizes only two phases, 0 and π. Itis therefore a type of ASK with f(t) taking the values −1 or 1.Quadrature phase-shift-keying (QPSK) has four phases, 0, π/2, π, and3π/2. M-ary PSK has M phases, given by 2πm/M with m=0, 1, . . . (M−1).Binary phase-shift keying is shown in FIG. 2B.

The Tag 14 encodes its Uplink Information Signal 40 as either an FM0baseband waveform or a Modified-Miller-subcarrier waveform. The FM0symbols and sequences are well defined in the EPCglobal UHF protocol andshown in FIGS. 3C and 3D. The FM0 baseband waveform inverts its phase atevery symbol boundary with the data-0 symbol having an additionalmid-symbol phase inversion. The Modified-Miller-subcarrier waveform issimilar in many respects to the Miller-subcarrier waveform defined inthe EPCglobal UHF protocol, but is modified such it can readily bedecoded in a manner similar to the FM0 waveforms. FIG. 4D illustratesthe symbols and sequences of the Modified-Miller-subcarrier waveform. Asshown in FIGS. 4A1 and 4A2, the Modified-Miller baseband waveforminverts its phase at every symbol boundary with the data-1 symbol havingan additional mid-symbol phase inversion. The Modified-Miller-subcarrierwaveform is generated by multiplying the Modified-Miller basebandwaveform with a square wave at M times the symbol rate as depicted inFIG. 4C. In this manner, the M=2 Modified-Miller-subcarrier waveformcontains 2 subcarrier cycles per bit, the M=4 Modified-Miller-subcarrierwaveform contains 4 subcarrier cycles per bit, and the M=8Modified-Miller-subcarrier waveform contains 8 subcarrier cycles perbit.

The receiver subsystem of the Interrogator 12, which is described belowin more detail, is capable of demodulating an ASK modulated carriersignal or a PSK modulated carrier signal. The receiver subsystemreceives the incoming modulated CW carrier signal and demodulates themodulated CW carrier signal to generate in-phase and quadrature signals.The binary levels of the in-phase and quadrature signals together withthe relevant timing information (e.g., the bit clock) are recoveredtherefrom to thereby reproduce the Uplink Information Signal 40. TheProcessor 16 recovers the Tag's reply message from the UplinkInformation Signal 40. The Processor 16 selects the uplink signalingscheme (FM0-type signaling or one of the threeModified-Miller-subcarrier-type signaling) and the data rate of theUplink Information Signal 40 by means of a command (i.e., Query command)communicated from the Interrogator 12 to the Tag 14 via the DownlinkInformation Signal 20.

The Interrogator 12 and the Tag 14 communicate with one another by apre-arranged signaling scheme whereby the Interrogator 12 transmits oneor more commands (referred to below as Interrogator-to-Tag signaling)and waits for certain replies from the one or more Tags of the system(referred to below as Tag-to-Interrogator signaling). Such replymessages can include randomly-generated data (RN16, which is 16 bitsrandomly-generated by the Tag), protocol control data (PC data field),identification data (EPC data) stored by the Tag, and error detectiondata (CRC data) generated by the Tag. More than one Tag may reply to anInterrogator's Query command. In this case, the Interrogator 12 mayresolve the collision and issue an ACK command to the selected Tag.Alternatively, the Interrogator 12 may not resolve the collision andissue a QueryAdjust, QueryRep or NAK command, which allows forarbitration of the collided Tags.

The Processor 16 initiates Interrogator-to-Tag signaling by cooperatingwith the Signal Source 22, Modulator 24 and Transmitter 26 to transmitvia the Antenna 28 a predetermined preamble waveform or a predeterminedframe-sync waveform. The preamble waveform comprises a fixed-lengthstart delimiter, a data-0 symbol, an RT calibration waveform, and a TRcalibration waveform as shown in FIG. 5A. The frame-sync waveform isidentical to the preamble waveform with the TR calibration waveformomitted as shown in FIG. 5B. In FIGS. 5A and 5B, “Tari” is a referencetime interval (preferably between 6.25 μs and 25 μs) forInterrogator-to-Tag downlink signaling and is the duration of the data-0symbol. The duration of the data-1 symbol is in a range between 1.5*Tariand 2.0*Tari. The pulse of the data-0 symbol and the data-1 symboloccurs at the end of the respective symbol with a pulsewidth PW that ispreferably less than 0.525*Tari and greater than the maximum of0.265*Tari and 2 μs. The duration of the RT calibration waveform isequal to the duration of the data-0 symbol plus the duration of a data-1symbol, which provides a total duration in a range between 2.5*Tari and3.0*Tari. The Tag measures the length of the RT calibration waveform anduses this measurement for interpreting subsequent symbols communicatedfrom the Interrogator to the Tag. The preamble waveform of FIG. 5Aprecedes each Query command transmitted from the Interrogator 12 to theTag 14. The frame-synch waveform of FIG. 5B precedes all other commands(e.g., Select, ACK, Read, Write, Kill) transmitted from the Interrogator12 to the Tag 14.

For uplink communications employing FM0-type signaling, the Tag 14initiates Tag-to-Interrogator signaling by generating one of the twopreambles shown in FIGS. 6A and 6B. The preamble selection is dictatedby the value of a predetermined bit (i.e., the TRext bit) in the Querycommand communicated from the Interrogator 12 to the Tag 14. The “v”shown in the FIGS. 6A and 6B indicates a signaling violation (i.e., aphase inversion should have occurred but did not). The end of the FM0Tag-to-Interrogator signaling ends with a “dummy” data-1 symbol as shownin FIG. 6C. The data rate of the FM0 Tag-to-Interrogator signaling canvary between 40 kbps and 640 kbps. This data rate is selected by theInterrogator by the length of the TR calibration waveform (FIG. 5A) anda predetermined bit (i.e., the DR bit) in the Query command communicatedfrom the Interrogator 12 to the Tag 14.

For uplink communication employing Modified-Miller-subcarrier signaling,the Tag 14 initiates Tag-to-Interrogator signaling by generating one ofthe six preambles shown in FIGS. 7A and 7B. The preamble selection isselected by the value of predetermined bits (i.e., the TRext bit and the2-bit M field) in the Query command communicated from the Interrogator12 to the Tag 14. The end of the Modified-Miller-subcarrier signalingends with a “dummy” data-1 symbol as shown in FIG. 7C. The data rate ofthe Modified-Miller-subcarrier signaling can vary between 5 kbps and 320kbps. This data rate is selected by the Interrogator 12 by the length ofthe TR calibration waveform (FIG. 5A) and predetermined bits (i.e., theDR bit and the 2-bit M field) in the Query command communicated from theInterrogator 12 to the Tag 14.

Returning back to FIG. 1, the receiver subsystem of the Interrogator 12employs homodyne detection wherein the modulated RF carrier signal isreceived at the Antenna 30 and amplified with a low noise amplifier 32whose output is mixed by a quadrature mixer 34 that uses the same RFsignal source 22 as the transmit functionality. The in-phase (I) andquadrature (Q) components output from the quadrature phase mixer 34 arelow-pass filtered (blocks 36A, 36B) to generate an in-phase signalr_(c)(t) and a quadrature signal r_(s)(t) that encode the FM0 waveformor the Modified-Miller-subcarrier waveform transmitted by the Tag 14. Adata recovery circuit 38 processes the r_(c)(t) and r_(s)(t) signals inorder to decode the FM0 waveform or Modified-Miller-subcarrier waveformtherein and recover the bit clock timing related thereto, therebyreproducing the Tag's Uplink Information Signal 40. The data recoverycircuit 38 can be realized in many different ways including analog,digital, and hybrid analog/digital implementations.

FIG. 8 illustrates an exemplary embodiment of a digital implementationof the data recovery circuit 38 for decoding the FM0 waveform andrecovering the symbol clock timing of the FM0 waveform according to theinvention. The data rate of the FM0 signaling can vary between 40 kbpsand 640 kbps. This data rate is selected by the Interrogator 12 by thelength of the TR calibration waveform (FIG. 5A) and a predetermined bit(i.e., the DR bit) in the Query command communicated from theInterrogator 12 to the Tag 14. The implementation includesanalog-to-digital conversion circuitry (blocks 702A, 702B) that samplethe r_(c)(t) and r_(s)(t) signals preferably at more than twice theNyquist frequency (i.e., more than twice the data rate of the FM0signaling, which can vary between 40 kbps and 640 kbps). In thepreferred embodiment, the r_(c)(t) and r_(s)(t) signals are sampled at asampling rate that is at least eight times the data rate of the FM0signaling. The in-phase samples and the quadrature phase samples, whichare each represented by a binary NRZ value {1, −1}, are stored in samplebuffers 704A and 704B, respectively. The in-phase samples and thequadrature phase samples are supplied to a symbol clock recovery block706 that processes the time-sequential samples to generate a symbolclock signal that is substantially synchronous to the transitionsbetween symbols in the FM0 waveform. Thus, the symbol clock signal has arate that corresponds to the data rate of the FM0 waveform. Such symbolclock recovery can be accomplished in many different ways well known inthe communications arts. More particularly, preamble processing isemployed for initial synchronization (including signal parameterestimation and symbol timing). Typically, a conventional correlationalgorithm (or a simple zero-crossing algorithm) provides preciseestimation of symbol timing. During data transmission, one or moresynchronization tracking algorithms may be used for timing adjustment.These algorithms are typically based on closed-looped estimators thatemploy narrow-bandwidth filtration. Details of these symbolsynchronization mechanisms is described in detail in Proakis, “DigitalCommunications”, McGraw-Hill, 2000, Section 6.3, herein incorporated byreference in its entirety.

The symbol stream encoded in the FM0 waveform can be logicallypartitioned into a sequence of odd/even symbol pairs. The even symbolscorrespond to particular in-phase samples r_(c)(2 k) of the r_(c) samplebuffer and also correspond to particular quadrature phase samplesr_(s)(2 k) of the r_(s) sample buffer, where k is an integer sequence 0,1, 2, 3, . . . . The odd symbols correspond to the particular in-phasesamples r_(c)(2 k+1) of the r_(c) sample buffer and also correspond toparticular quadrature phase samples r_(s)(2 k+1) of the r_(s) samplebuffer. In the preferred embodiment where the r_(c)(t) and r_(s)(t)signals are sampled at eight times the data rate of the FM0 signaling,each odd symbol corresponds to eight successive in-phase samples andeight successive quadrature phase samples, while each even symbolcorresponds to the next eight successive in-phase samples and the nexteight successive quadrature phase samples. For each odd/even symbolpair, the odd symbol occurs within a time interval between 0 and T andthe even symbol occurs within a time interval between T and 2 T. Theduration of these time intervals is inversely proportional to the datarate of the FM0 waveform, which is selected by downlink communicationfrom the Interrogator 12 to the Tag 14.

The symbol clock signal generated by the symbol clock recovery block 706is used in eight signal processing paths that operate to decode anodd/even symbol pair in parallel. Four of the eight paths process thein-phase samples (block 710A) while the other four paths process thequadrature phase samples (block 710B).

The four paths that process the in-phase samples (block 710A) can belogically divided into two groups with two paths per group. In accordwith the invention, one group operates on in-phase samples that fallwithin an extended processing window corresponding to the −T/2 to 3 T/2time interval for the odd symbol of the pair (blocks 712A1 and 712A2).The other group operates on in-phase samples that fall within anextended processing window corresponding to the T/2 to 5 T/2 timeinterval for the even symbol of the pair (blocks 712A3 and 712A4).

Similarly, the four paths that process the quadrature phase samplesr_(s)(k) (block 710B) can be logically divided into two groups with twopaths per group. One group (not shown) operates on quadrature phasesamples that fall within an extended processing window corresponding tothe −T/2 to 3 T/2 time interval for the odd symbol of the pair. Theother group (not shown) operates on quadrature phase samples that fallwithin an extended processing window corresponding to the T/2 and 5 T/2time interval for the even symbol of the pair.

In the first path (blocks 712A1 and 714A1), the in-phase samples thatfall within the −T/2 to 3 T/2 processing window are samplewisemultiplied by an S₀-odd reference waveform. In the digital domain (block712A1), these operations are carried out by changing the sign of thein-phase samples in accordance with the value of the corresponding partof the S₀-odd reference waveform (FIG. 9B) as follows:

Sample Reference Waveform Sign-adjusted Sample −1 −1  1 (Sign Flips) −11 −1 (No Change) 1 −1 −1 (Sign Flips) 1 1  1 (No Change)The results of the samplewise multiplication are accumulated. In thedigital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to 3 T/2 processing window.The result of the accumulation denoted Z_(c0) odd is then squared inblock 714A1. Alternatively, the absolute value of the accumulationresult Z_(c0) odd may be calculated in block 714A1.

In the second path (blocks 712A2 and 714A2), the in-phase samples thatfall within the −T/2 to 3 T/2 processing window are samplewisemultiplied by an S₁-odd reference waveform (FIG. 10B). In the digitaldomain (block 712A2), these operations are carried out by changing thesign of the in-phase samples in accordance with the value of thecorresponding part of the S₁-odd reference waveform as set forth above.The results of the samplewise multiplication are accumulated. In thedigital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to 3 T/2 processing window.The result of the accumulation denoted Z_(c1) odd is then squared inblock 714A2. Alternatively, the absolute value of the accumulationresult Z_(c1) odd may be calculated in block 714A2.

In the third path (blocks 712A3 and 714A3), the in-phase samples thatfall within the T/2 to 5 T/2 processing window are samplewise multipliedby the S₀-even reference waveform (FIG. 9C). In the digital domain(block 712A3), these operations are carried out by changing the sign ofthe in-phase samples in accordance with the value of the correspondingpart of the S₀-even reference waveform as set forth above. The resultsof the samplewise multiplication are accumulated. In the digital domain,this operation is carried out by summing the sign-adjusted in-phasesamples over the T/2 to 5 T/2 processing window. The result of theaccumulation denoted Z_(c0) even is then squared in block 714A3.Alternatively, the absolute value of the accumulation result Z_(c0) evenmay be calculated in block 714A3.

In the fourth path (blocks 712A4 and 714A4), the in-phase samples thatfall within the T/2 to 5 T/2 processing window are samplewise multipliedby an S₁-even reference waveform (FIG. 10C). In the digital domain(block 712A4), these operations are carried out by changing the sign ofthe in-phase samples in accordance with the value of the correspondingpart of the S₁-even reference waveform as set forth above. The resultsof the samplewise multiplication are accumulated. In the digital domain,this operation is carried out by summing the sign-adjusted in-phasesamples over the T/2 to 5 T/2 processing window. The result of theaccumulation denoted Z_(c1) even is then squared in block 714A4.Alternatively, the absolute value of the accumulation result Z_(c1) evenmay be calculated in block 714A4.

In block 710B, the operations of blocks 712A1 to 714A4 as describedabove are performed on corresponding quadrature samples to therebyrealize the other four processing paths.

The S₀-odd reference waveform (which is a window of the composite S₀reference waveform shown in FIG. 9A) is shown in FIG. 9B. Note that theS₀-odd reference waveform is a square wave that corresponds to the FM0data-0 symbol of FIG. 3A1 over the time interval between 0 and T with aphase inversion for the interval 0 to −T/2 and a phase inversion in theinterval from T to 3 T/2. In this manner, the S₀-odd reference waveformmaintains the FM0 signaling rule that a phase inversion occur at thesymbol boundaries.

The S₀-even reference waveform (which is a different window of thecomposite S₀ reference waveform) is shown in FIG. 9C. Note that theS₀-even reference waveform is a square wave that corresponds to the FM0data-0 symbol of FIG. 3A1 over the time interval between T and 2 T witha phase inversion for the interval T to T/2 and a phase inversion in theinterval from 2 T to 5 T/2. In this manner, the S₀-even referencewaveform maintains the FM0 signaling rule that a phase inversion occurat the symbol boundaries.

FIG. 9A shows the composite S₀ reference waveform for FM0 signaling,which is the composite of the S₀-odd reference waveform (FIG. 9B) andthe S₀-even reference waveform (FIG. 9C).

The S₁-odd reference waveform (which is a window of the composite S₁reference waveform shown in FIG. 10A) is shown in FIG. 10B. Note thatthe S₁-odd reference waveform is a square wave that corresponds to theFM0 data-1 symbol of FIG. 3A2 over the time interval between 0 and Twith a phase inversion for the interval 0 to −T/2 and a phase inversionin the interval from T to 3 T/2. In this manner, the S₁-odd referencewaveform maintains the FM0 signaling rule that a phase inversion occurat the symbol boundaries.

The S₁-even reference waveform (which is a different window of thecomposite S₁ reference waveform) is shown in FIG. 10C. Note that theS₁-even reference waveform is a square wave that corresponds to the FM0data-1 symbol of FIG. 3A2 over the time interval between T and 2 T witha phase inversion for the interval T to T/2 and a phase inversion in theinterval from 2 T to 5 T/2. In this manner, the S₁-even referencewaveform maintains the FM0 signaling rule that a phase inversion occurat the symbol boundaries.

FIG. 10A shows the composite S₁ reference waveform, which is thecomposite of the S₁-odd reference waveform (FIG. 10B) and the S₁-evenreference waveform (FIG. 10C).

In essence, the samplewise multiplication and accumulation operationscarried out in each one of the eight processing paths of blocks 710A and710B are digital equivalents of a matched filter implementation over atwo symbol period (i.e., over a 2 T period). The squaring function (orabsolute value function) maps the accumulation results of eachrespective path into positive numbers such the accumulation results canbe effectively combined. The outputs of the squaring functions (orabsolute value functions) from complementary paths are summed together.In this manner, block 716A sums the squared accumulation results (or theabsolute value of such accumulated results) for the Z_(c0) oddprocessing path (blocks 712A1 and 714A1) and the Z_(s0) odd processingpath (not shown) in block 710B, block 716B sums the squared accumulationresults (or the absolute value of such accumulation results) for theZ_(c1) odd processing path (blocks 712A2 and 714A2) and the Z_(s1) oddprocessing path (not shown) in block 710B, block 716C sums the squareaccumulation results (or the absolute value of such accumulationresults) for the Z_(c0) even processing path (blocks 712A3 and 714A3)and the Z_(s0) even processing path (not shown) in block 710B, and block716D sums the squared accumulation results (or the absolute value ofsuch accumulation results) for the Z_(C1) even processing path (blocks712A4 and 714A4) and the Z_(s1) even processing path (not shown) inblock 710B.

The output (Z0odd) of adder block 716A and the output (Z1odd) of adderblock 716B are supplied to comparison logic 718A that assigns a binaryvalue of 0 or 1 for the odd symbol based thereon. Such assignment ispreferably realized by the following comparison operations:

if (Z0odd > Z1odd), then the odd symbol is assigned to binary value 0;else the odd symbol is assigned to binary value 1 endif; where Z0odd isthe output of the adder block 716A and Z1odd is the output of the adderblock 716B.

Similarly, the output (Z0even) of adder block 716C and the output(Z1even) of adder block 716D are supplied to comparison logic 718B thatassigns a binary value of 0 or 1 for the even symbol based thereon. Suchassignment is preferably realized by the following comparisonoperations:

if (Z0even > Z1even), then the even symbol is assigned to binary value0; else the even symbol is assigned to binary value 1 endif; whereZ0even is the output of the adder block 716C and Z1even is the output ofthe adder block 716D.

Controls signals, which are synchronized to the symbol clock timing, aresupplied by the symbol clock recovery block 706 to multiplexers 720A,720B such that odd bit value is output for the odd symbol time period (0to T) and the even bit value is output for the even symbol time period(T to 2 T). In this manner, the output of the multiplexers 720A, 720Bprovides bit estimates for each odd/even symbol pair in the Tag's UplinkInformation Signal 40.

The bit estimates output by the multiplexers 720A, 720B may optionallybe loaded into a post-processing block (not shown) that processes theestimates to cancel interference (such as co-channel interference ormulti-path interference), an example of which is set forth in US2004/0014424 to Kristensson et al, herein incorporated by reference inits entirety. Such post-processing may also provide for errorcorrection, which is typically realized by Reed-Solomon decoding orconvolutional decoding as part of Viterbi processing.

After data recovery is complete, the bit stream that represents theTag's Uplink Information Signal 40 is stored in a buffer forcommunication to the processor 16 for subsequent processing.

The data processing blocks of FIG. 8 are preferably part of a digitalsignal processing platform 721, which may be realized by a digitalsignal processor, an FPGA, an ASIC or other suitable data processingmeans.

FIGS. 11A through 11E illustrate the signal processing operations of thedata recovery circuit of FIG. 8.

FIG. 11A illustrates an ideal r_(c)(t) signal that encodes an odd/evensymbol pair {0,1}.

FIG. 11B illustrates the composite S₀ reference waveform for FM0-typesignaling (FIG. 9A). Samples of the r_(c)(t) signal that are receivedwithin the −T/2 to 3 T/2 processing window are samplewise multiplied(e.g., sign changed) by the portion of the composite S₀ referencewaveform of FIG. 9A for the time interval between −T/2 and 3 T/2 (i.e.,the S₀-odd reference waveform of FIG. 9B) and the results accumulated togenerate the Z_(c0)odd signal as shown in FIG. 11C. Samples of ther_(c)(t) signal that are received within the T/2 to 5 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by the portion ofthe composite S₀ reference waveform of FIG. 9A for the time intervalbetween T/2 and 5 T/2 (i.e., the S₀-even reference waveform of FIG. 9C)and the results accumulated to generate the Z_(c0)even signal as shownin FIG. 11C.

FIG. 11D illustrates the composite S₁ reference waveform for FM0-typesignaling (FIG. 10A). Samples of the r_(c)(t) signal that are receivedwithin the −T/2 to 3 T/2 processing window are samplewise multiplied(e.g., sign changed) by the portion of the composite S₁ referencewaveform of FIG. 10A for the time interval between −T/2 and 3 T/2 (i.e.,the S₁-odd reference waveform of FIG. 10B) and the results accumulatedto generate the Z_(c1)odd signal as shown in FIG. 11E. Samples of ther_(c)(t) signal that are received within the T/2 to 5 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by the portion ofthe composite S₁ reference waveform of FIG. 10A for the time intervalbetween T/2 and 5 T/2 (i.e., the S₁-even reference waveform of FIG. 10C)and the results accumulated to generate the Z_(c1)even signal as shownin FIG. 11D.

The signal processing operations of blocks 710A and 710B generatecomplementary results. In other words, Z_(s0)odd corresponds toZ_(c1)odd, Z_(s1)odd corresponds to Z_(c0)odd, Z_(s0)even corresponds toZ_(c1)even, and Z_(s1)even corresponds to Z_(c0)even. The signal levelof the accumulation results at the end of the respective processingwindows (at 3 T/2 or 5 T/2) are mapped to positive values by squaring(or by absolute value functions) and then summed together incomplementary pairs. The result sums are then used as input to thecomparison logic for bit level assignment.

FIG. 12 illustrates an analog implementation of the data recoverycircuit of FIG. 8 with like numerals designating analog-forms of thesignal processing functionality described above. Note that in the analogimplementation, the samplewise multiplication operations are carried outby analog multipliers and the accumulation operations are carried out byintegration circuitry.

FIG. 13 illustrates an alternate digital implementation for the datarecovery circuit 38 for decoding the FM0 waveform and recovering the bitclock timing of the FM0 waveform. The implementation includesanalog-to-digital conversion circuitry (blocks 702A″, 702B″) that samplethe r_(c)(t) and r_(s)(t) signals at preferably more than twice theNyquist frequency (i.e., more than twice the data rate of the FM0signaling, which can vary between 40 kbps and 640 kbps). In thepreferred embodiment, the r_(c)(t) and r_(s)(t) signals are sampled ateight times the data rate of the FM0 signaling. The in-phase samples andthe quadrature phase samples, which are each represented by a binary NRZvalue {1, −1}, are stored in sample buffers 704A″ and 704B″,respectively. The in-phase samples and the quadrature phase samples aresupplied to a symbol clock recovery block 706″ that processes thetime-sequential samples to generate a symbol clock signal that issubstantially synchronous to the transitions between symbols in the FM0waveform. Thus, the symbol clock signal has a rate that corresponds tothe data rate of the FM0 waveform. Such symbol clock recovery can beaccomplished in many different ways well known in the communicationsarts as described above. The symbol clock signal generated by the symbolclock recovery block 706″ is used in four signal processing paths thatoperate to decode symbols. Two of the four paths process the in-phasesamples (block 732A) while the other two paths process the quadraturephase samples (block 732B).

In the first path of block 732A (blocks 734A1, 736A1, 738A1, 740A1), thein-phase samples that fall within the −T/2 to T/2 processing window aresamplewise multiplied by the S₀ reference waveform of FIG. 9A. In thedigital domain (block 734A1), these operations are carried out bychanging the sign of the in-phase samples in accordance with the valueof the corresponding part of the S₀ reference waveform as follows:

Sample Reference Waveform Sign-adjusted Sample −1 −1  1 (Sign Flips) −11 −1 (No Change) 1 −1 −1 (Sign Flips) 1 1  1 (No Change)The results of the samplewise multiplication are accumulated. In thedigital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to T/2 processing window.The result of the accumulation of block 734A1 is stored in a storagecell in block 736A1. The accumulation results written to the storagecell in the previous processing window (the time interval −3 T/2 to−T/2) are output and added to the accumulation results for the currentprocessing window (the time interval −T/2 to T/2) in block 738A1. Thesum denoted Z_(c0) is then squared in block 740A1. Alternatively, theabsolute value of the sum Z_(c0) may be calculated in block 740A1.

In the second path (blocks 734A2, 736A2, 738A2, 740A2), the in-phasesamples that fall within the −T/2 to T/2 processing window aresamplewise multiplied by the S₁ reference waveform of FIG. 10B. In thedigital domain (block 734A2), these operations are carried out bychanging the sign of the in-phase samples in accordance with the valueof the corresponding part of the S₁ reference waveform as describedabove. The results of the samplewise multiplication are accumulated. Inthe digital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to T/2 processing window.The result of the accumulation of block 734A2 is stored in a storagecell in block 736A2. The accumulation results written to the storagecell in the previous processing window (the time interval −3 T/2 to−T/2) are output and added to the accumulation results for the currentprocessing window (the time interval −T/2 to T/2) in block 738A2. Thesum denoted Z_(c1) is then squared in block 740A2. Alternatively, theabsolute value of the sum Z_(c1) may be calculated in block 740A2.

In block 732B, the operations of blocks 734A1 to 740A2 as describedabove are performed on corresponding quadrature samples to therebyrealize the other two processing paths.

The S₀ reference waveform is shown in FIG. 9A. The S₁ reference waveformis shown in FIG. 10A. In essence, the multiplication, accumulation andstorage cell access operations carried out in each one of the fourprocessing paths of blocks 732A and 732B are digital equivalents of amatched filter implementation over a two symbol period (i.e., over a 2 Tperiod) which is dictated by two successive processing windows thatextend from −T/2 to 3 T/2. The squaring function (or absolute valuefunction) maps the accumulation results of each respective path intopositive numbers such the accumulation results can be effectivelycombined. The outputs of the squaring functions (or absolute valuefunctions) from complementary paths are summed together. In this manner,block 742A sums the squared accumulation results (or the absolute valueof such accumulated results) for the Z_(c0) processing path (blocks734A1, 736A1, 738A1, 740A1) and the Z_(s0) processing path (not shown)in block 732B, and block 742B sums the squared accumulation results (orthe absolute value of such accumulation results) for the Z_(c1)processing path (blocks 734A2, 736A2, 738A2, 740A2) and the Z_(s1)processing path (not shown) in block 732B.

The output (Z0) of adder block 742A and the output (Z1) of adder block742B are supplied to comparison logic 744 that assigns a binary value of0 or 1 for the current symbol based thereon. Such assignment ispreferably realized by the following comparison operations:

if (Z0 > Z1), then the current symbol is assigned to binary value 0;else the current symbol is assigned to binary value 1 endif; where Z0 isthe output of the adder block 742A and Z1 is the output of the adderblock 742B.

Controls signals, which are synchronized to the symbol clock timing, aresupplied by the symbol clock recovery block 706″ to multiplexer 746 suchthat bit value is output for the current symbol time period (0 to T).Such operations are repeated for successive processing windows. In thismanner, the output of the multiplexer 746 provides bit estimates forsuccessive symbols in the Tag's Uplink Information Signal 40.

The bit estimates output by the multiplexer 746 may optionally be loadedinto a post-processing block (not shown) that processes the estimates tocancel interference (such as co-channel interference or multi-pathinterference) as described above.

FIG. 14 illustrates an exemplary embodiment of a digital implementationof the data recovery circuit 38 for decoding theModified-Miller-subcarrier signaling waveforms and recovering the symbolclock timing of the Modified-Miller-subcarrier signaling waveformsaccording to the invention. The data rate of theModified-Miller-subcarrier signaling can vary between 5 kbps and 320kbps. This data rate is selected by the Interrogator 12 by the length ofthe TR calibration waveform (FIG. 5A) and predetermined bits (i.e., theDR bit and the 2-bit M field) in the Query command communicated from theInterrogator 12 to the Tag 14. The implementation includesanalog-to-digital conversion circuitry (blocks 1702A, 1702B) that samplethe r_(c)(t) and r_(s)(t) signals preferably at more than twice theNyquist frequency (i.e., more than twice the data rate of theModified-Miller-subcarrier signaling, which can vary between 5 kbps and320 kbps). In the preferred embodiment, the r_(c)(t) and r_(s)(t)signals are sampled at a sampling rate that is at least eight times themaximum data rate of the Modified-Miller-subcarrier signaling (i.e.,eight times the maximum date rate of 320 kbps). Alternatively, thesampling rate can be controlled in accordance with the selected M value(i.e., 2/4/8) such that it is at least eight times the data rate of theselected Modified-Miller-subcarrier signaling scheme. The in-phasesamples and the quadrature phase samples, which are each represented bya binary NRZ value {1, −1}, are stored in sample buffers 1704A and1704B, respectively. The in-phase samples and the quadrature phasesamples are supplied to a clock recovery block 1706 that processes thetime-sequential samples to generate a subcarrier clock signal that issubstantially synchronous to the transitions in theModified-Miller-subcarrier waveform. Thus, the subcarrier clock signalhas a rate that corresponds to the data rate of theModified-Miller-subcarrier waveform. Such clock recovery operations canbe accomplished in many different ways well known in the communicationsarts. More particularly, preamble processing is employed for initialsynchronization (including signal parameter estimation and symboltiming). Typically, a conventional correlation algorithm (or a simplezero-crossing algorithm) provides precise estimation of timing. Duringdata transmission, one or more synchronization tracking algorithms maybe used for timing adjustment. These algorithms are typically based onclosed-looped estimators that employ narrow-bandwidth filtration.Details of these synchronization mechanisms are described in detail inProakis, “Digital Communications”, McGraw-Hill, 2000, Section 6.3,herein incorporated by reference in its entirety. The symbol clocksignal, which is substantially synchronous to symbol transitions in theModified-Miller-subcarrier waveform, is derived by up-converting thesubcarrier clock signal by a factor (i.e., 2, 4, or 8) corresponding tothe M value of the selected Modified-Miller-subcarrier signaling scheme.

The symbol stream encoded in the Modified-Miller-subcarrier waveform canbe logically partitioned into a sequence of odd/even symbol pairs. Theeven symbols correspond to particular in-phase samples r_(c)(2 k) of ther_(c) sample buffer and also correspond to particular quadrature phasesamples r_(c)(2 k) of the r_(c) sample buffer, where k is an integersequence 0, 1, 2, 3, . . . . The odd symbols correspond to theparticular in-phase samples r_(c)(2 k+1) of the r_(c) sample buffer andalso correspond to particular quadrature phase samples r_(s)(2 k+1) ofthe r_(s) sample buffer. For example, where the r_(c)(t) and r_(s)(t)signals are sampled at eight times the data rate of the selectedModified-Miller-subcarrier signaling scheme, each odd symbol correspondsto eight successive in-phase samples and eight successive quadraturephase samples, while each even symbol corresponds to the next eightsuccessive in-phase samples and the next eight successive quadraturephase samples. For each odd/even symbol pair, the odd symbol occurswithin a time interval between 0 and T and the even symbol occurs withina time interval between T and 2 T. The duration of these time intervalsis inversely proportional to the data rate of theModified-Miller-subcarrier waveform, which is selected by downlinkcommunication from the Interrogator 12 to the Tag 14.

The subcarrier clock signal and the symbol clock signal generated by theclock recovery block 1706 is used in eight signal processing paths thatoperate to decode an odd/even symbol pair in parallel. Four of the eightpaths process the in-phase samples (block 1710A) while the other fourpaths process the quadrature phase samples (block 1710B).

The four paths that process the in-phase samples (block 1710A) can belogically divided into two groups with two paths per group. In accordwith the invention, one group operates on in-phase samples that fallwithin an extended processing window corresponding to the −T/2 to 3 T/2time interval for the odd symbol of the pair (blocks 1712A1 and 1712A2).The other group operates on in-phase samples that fall within anextended processing window corresponding to the T/2 to 5 T/2 timeinterval for the even symbol of the pair (blocks 1712A3 and 1712A4).

Similarly, the four paths that process the quadrature phase samplesr_(s)(k) (block 1710B) can be logically divided into two groups with twopaths per group. One group (not shown) operates on quadrature phasesamples that fall within an extended processing window corresponding tothe −T/2 to 3 T/2 time interval for the odd symbol of the pair. Theother group (not shown) operates on quadrature phase samples that fallwithin an extended processing window corresponding to the T/2 and 5 T/2time interval for the even symbol of the pair.

In the first path (blocks 1712A1 and 1714A1), the in-phase samples thatfall within the −T/2 to 3 T/2 processing window are samplewisemultiplied by an S₀ reference waveform generated by block 1706. The S₀reference waveform generated by block 1706 varies based upon the M value(e.g., 2, 4 or 8) of the selected Modified-Miller-subcarrier signalingscheme as shown in FIGS. 15C1, 15D1 and 15E1. In the digital domain, theoperations of block 1712A1 are carried out by changing the sign of thein-phase samples in accordance with the value of the corresponding partof the S₀ reference waveform as follows:

Sample Reference Waveform Sign-adjusted Sample −1 −1  1 (Sign Flips) −11 −1 (No Change) 1 −1 −1 (Sign Flips) 1 1  1 (No Change)The results of the samplewise multiplication are accumulated. In thedigital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to 3 T/2 processing window.The result of the accumulation denoted Z_(c0) odd is then squared inblock 714A1. Alternatively, the absolute value of the accumulationresult Z_(c0) odd may be calculated in block 714A1.

In the second path (blocks 1712A2 and 1714A2), the in-phase samples thatfall within the −T/2 to 3 T/2 processing window are samplewisemultiplied by an S₁ reference waveform generated by block 1706. The S₁reference waveform generated by block 1706 varies based upon the M value(e.g., 2, 4 or 8) of the selected Modified-Miller-subcarrier signalingscheme as shown in FIGS. 15C2, 15D2 and 15E2. In the digital domain, theoperations of block 1712A2 are carried out by changing the sign of thein-phase samples in accordance with the value of the corresponding partof the S₁ reference waveform as set forth above. The results of thesamplewise multiplication are accumulated. In the digital domain, thisoperation is carried out by summing the sign-adjusted in-phase samplesover the −T/2 to 3 T/2 processing window. The result of the accumulationdenoted Z_(c1) odd is then squared in block 714A2. Alternatively, theabsolute value of the accumulation result Z_(c1) odd may be calculatedin block 714A2.

In the third path (blocks 1712A3 and 1714A3), the in-phase samples thatfall within the T/2 to 5 T/2 processing window are samplewise multipliedby the S₀ reference waveform generated by block 1706. In the digitaldomain, the operations of block 1712A3 are carried out by changing thesign of the in-phase samples in accordance with the value of thecorresponding part of the S₀ reference waveform as set forth above. Notethat the S₀ reference waveforms of FIGS. 15C1, 15D1 and 15E1 depict the−T/2 to 3 T/2 processing window. The S₀ reference waveforms for the T/2to 5 T/2 processing window can be derived by following the waveforms ofFIGS. 15C1, 15D1 and 15E1 for the period T/2 to 3 T/2 and then wrappingback to include the waveform shown for the period −T/2 to T/2. Theresults of the samplewise multiplication are accumulated. In the digitaldomain, this operation is carried out by summing the sign-adjustedin-phase samples over the T/2 to 5 T/2 processing window. The result ofthe accumulation denoted Z_(c0) even is then squared in block 1714A3.Alternatively, the absolute value of the accumulation result Z_(c0) evenmay be calculated in block 1714A3.

In the fourth path (blocks 1712A4 and 1714A4), the in-phase samples thatfall within the T/2 to 5 T/2 processing window are samplewise multipliedby the S₁ reference waveform generated by block 1706. In the digitaldomain, the operations of block 1712A4 are carried out by changing thesign of the in-phase samples in accordance with the value of thecorresponding part of the S₁ reference waveform as set forth above. Notethat the S₁ reference waveforms of FIGS. 15C2, 15D2 and 15E2 depict the−T/2 to 3 T/2 processing window. The S₁ reference waveforms for the T/2to 5 T/2 processing window can be derived by following the waveforms ofFIGS. 15C2, 15D2 and 15E2 for the period T/2 to 3 T/2 and then wrappingback to include the waveform shown for the period −T/2 to T/2. Theresults of the samplewise multiplication are accumulated. In the digitaldomain, this operation is carried out by summing the sign-adjustedin-phase samples over the T/2 to 5 T/2 processing window. The result ofthe accumulation denoted Z_(c1) even is then squared in block 1714A4.Alternatively, the absolute value of the accumulation result Z_(c1) evenmay be calculated in block 1714A4.

In block 1710B, the operations of blocks 1712A1 to 1714A4 as describedabove are performed on corresponding quadrature samples to therebyrealize the other four processing paths.

The S₀ reference waveforms generated by block 1706 for the different Mvalues (e.g., 2, 4 or 8) of the Modified-Miller-subcarrier signalingscheme are shown in FIGS. 15C1, 15D1 and 15E1. Each S₀ referencewaveform is derived by multiplying the S₀ basis waveform of FIG. 15A1 bya square wave as shown in FIG. 15B. The S₀ basis waveform is equivalentto the symbol clock signal. The square wave is equivalent to thesubcarrier clock signal and thus its rate is dependent on the M value ofthe selected Modified-Miller-subcarrier signaling scheme. Note that theS₀ basis waveform corresponds to the data-0 symbol of Modified-Millerbaseband signal over the time interval between 0 and T with a phaseinversion at the symbol boundaries (0, T). In this manner, the S₀ basiswaveform maintains the signaling rule that a phase inversion occur atthe symbol boundaries.

The S1 reference waveforms generated by block 1706 for the different Mvalues (e.g., 2, 4 or 8) of the Modified-Miller-subcarrier signalingscheme are shown in FIGS. 15C2, 15D2 and 15E2. Each S₁ referencewaveform is derived by multiplying the S₁ basis waveform of FIG. 15A2 bya square wave as shown in FIG. 15B. The S₀ basis waveform is equivalentto the symbol clock signal. The square wave is equivalent to thesubcarrier clock signal and thus its rate is dependent on the M value ofthe selected Modified-Miller-subcarrier signaling scheme. Note that theS₁ basis waveform corresponds to the data-1 symbol of Modified-Millerbaseband signal over the time interval between 0 and T with a phaseinversion at the symbol boundaries (0, T). In this manner, the S₁ basiswaveform maintains the signaling rule that a phase inversion occur atthe symbol boundaries.

In essence, the samplewise multiplication and accumulation operationscarried out in each one of the eight processing paths of blocks 1710Aand 1710B are digital equivalents of a matched filter implementationover a two symbol period (i.e., over a 2 T period). The squaringfunction (or absolute value function) maps the accumulation results ofeach respective path into positive numbers such the accumulation resultscan be effectively combined. The outputs of the squaring functions (orabsolute value functions) from complementary paths are summed together.In this manner, block 1716A sums the squared accumulation results (orthe absolute value of such accumulated results) for the Z_(c0) oddprocessing path (blocks 1712A1 and 1714A1) and the Z_(s0) odd processingpath (not shown) in block 1710B, block 1716B sums the squaredaccumulation results (or the absolute value of such accumulationresults) for the Z_(c1) odd processing path (blocks 1712A2 and 1714A2)and the Z_(s1) odd processing path (not shown) in block 1710B, block1716C sums the square accumulation results (or the absolute value ofsuch accumulation results) for the Z_(c0) even processing path (blocks1712A3 and 1714A3) and the Z_(s0) even processing path (not shown) inblock 1710B, and block 1716D sums the squared accumulation results (orthe absolute value of such accumulation results) for the Z_(c1) evenprocessing path (blocks 1712A4 and 1714A4) and the Z_(s1) evenprocessing path (not shown) in block 1710B.

The output (Z0odd) of adder block 1716A and the output (Z1odd) of adderblock 1716B are supplied to comparison logic 1718A that assigns a binaryvalue of 0 or 1 for the odd symbol based thereon. Such assignment ispreferably realized by the following comparison operations:

if (Z0odd > Z1odd), then the odd symbol is assigned to binary value 0;else the odd symbol is assigned to binary value 1 endif; where Z0odd isthe output of the adder block 1716A and Z1odd is the output of the adderblock 1716B.

Similarly, the output (Z0even) of adder block 1716C and the output(Z1even) of adder block 1716D are supplied to comparison logic 1718Bthat assigns a binary value of 0 or 1 for the even symbol based thereon.Such assignment is preferably realized by the following comparisonoperations:

if (Z0even > Z1even), then the even symbol is assigned to binary value0; else the even symbol is assigned to binary value 1 endif; whereZ0even is the output of the adder block 1716C and Z1even is the outputof the adder block 1716D.

Controls signals, which are synchronized to the symbol clock timing, aresupplied by the clock recovery block 1706 to multiplexers 1720A, 1720Bsuch that odd bit value is output for the odd symbol time period (0 toT) and the even bit value is output for the even symbol time period (Tto 2 T). In this manner, the output of the multiplexers 1720A, 1720Bprovides bit estimates for each odd/even symbol pair in the Tag's UplinkInformation Signal 40.

The bit estimates output by the multiplexers 1720A, 1720B may optionallybe loaded into a post-processing block (not shown) that processes theestimates to cancel interference (such as co-channel interference ormulti-path interference), an example of which is set forth in US2004/0014424 to Kristensson et al, herein incorporated by reference inits entirety. Such post-processing may also provide for errorcorrection, which is typically realized by Reed-Solomon decoding orconvolutional decoding as part of Viterbi processing.

After data recovery is complete, the bit stream that represents theTag's Uplink Information Signal 40 is stored in a buffer forcommunication to the processor 16 for subsequent processing.

The data processing blocks of FIG. 14 are preferably part of a digitalsignal processing platform 1721, which may be realized by a digitalsignal processor, an FPGA, an ASIC or other suitable data processingmeans.

FIGS. 16A1 through 16A5 illustrate the signal processing operations ofthe data recovery circuit of FIG. 14 for the particular symbol sequence{0,0,x}, where x represents a don't care symbol (i.e., either a data-0symbol or a data-1 symbol). These signal processing operations recoverthe “0” bit value for the middle odd symbol of the sequence. Similarprocessing operations are performed to recover the bit values of thepreceding and subsequent even symbols.

FIG. 16A1 illustrates an ideal r_(c)(t) signal utilizing the M=2Modified-Miller-subcarrier signaling scheme that encodes the symbolsequence {0,0,x}.

FIG. 16A2 illustrates the S₀ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C1). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₀ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c0) signal as shown in FIG. 16A3.

FIG. 16A4 illustrates the S₁ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C2). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₁ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c1) signal as shown in FIG. 16A5.

Similar operations are performed on samples of the quadrature r_(s)(t)signal that are received within the −T/2 to 3 T/2 processing window.These signal processing operations (blocks 1710A and 1710B) generatecomplementary results. In other words, Z_(c0) corresponds to Z_(s1) andZ_(c1) corresponds to Z_(s0). The signal level of the accumulationresults at the end of the processing window (at 3 T/2) are mapped topositive values by squaring (or by absolute value functions) and thensummed together in pairs. The result sums are then used as input to thecomparison logic for bit level assignment, which recovers the “0” bitlevel for the middle data-0 symbol in the {0,0,x} symbol sequence.

FIGS. 16B1 through 16B5 illustrate the signal processing operations ofthe data recovery circuit of FIG. 14 for the particular symbol sequence{1,0,x}, where x represents a don't care symbol (i.e., either a data-0symbol or a data-1 symbol). These signal processing operations recoverthe “0” bit value for the middle odd symbol of the sequence. Similarprocessing operations are performed to recover the bit values of thepreceding and subsequent even symbols.

FIG. 16B1 illustrates an ideal r_(c)(t) signal utilizing the M=2Modified-Miller-subcarrier signaling scheme that encodes the symbolsequence {1,0,x}.

FIG. 16B2 illustrates the S₀ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C1). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₀ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c0) signal as shown in FIG. 16B3.

FIG. 16B4 illustrates the S₁ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C2). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₁ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c1) signal as shown in FIG. 16B5.

Similar operations are performed on samples of the quadrature r_(s)(t)signal that are received within the −T/2 to 3 T/2 processing window.These signal processing operations (blocks 1710A and 1710B) generatecomplementary results. In other words, Z_(c0) corresponds to Z_(s1) andZ_(c1) corresponds to Z_(s0). The signal level of the accumulationresults at the end of the processing window (at 3 T/2) are mapped topositive values by squaring (or by absolute value functions) and thensummed together in pairs. The result sums are then used as input to thecomparison logic for bit level assignment, which recovers the “0” bitlevel for the middle data-0 symbol in the {1,0,x} symbol sequence.

FIGS. 16C1 through 16C5 illustrate the signal processing operations ofthe data recovery circuit of FIG. 14 for the particular symbol sequence{0,1,x}, where x represents a don't care symbol (i.e., either a data-0symbol or a data-1 symbol). These signal processing operations recoverthe “1” bit value for the middle odd symbol of the sequence. Similarprocessing operations are performed to recover the bit values of thepreceding and subsequent even symbols.

FIG. 16C1 illustrates an ideal r_(c)(t) signal utilizing the M=2Modified-Miller-subcarrier signaling scheme that encodes the symbolsequence {0,1,x}.

FIG. 16A2 illustrates the S₀ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C1). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₀ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c0) signal as shown in FIG. 16C3.

FIG. 16C4 illustrates the S₁ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C2). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₁ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c1) signal as shown in FIG. 16C5.

Similar operations are performed on samples of the quadrature r_(s)(t)signal that are received within the −T/2 to 3 T/2 processing window.These signal processing operations (blocks 1710A and 1710B) generatecomplementary results. In other words, Z_(c0) corresponds to Z_(s1) andZ_(c1) corresponds to Z_(s0). The signal level of the accumulationresults at the end of the processing window (at 3 T/2) are mapped topositive values by squaring (or by absolute value functions) and thensummed together in pairs. The result sums are then used as input to thecomparison logic for bit level assignment, which recovers the “1” bitlevel for the middle data-1 symbol in the {0,1,x} sequence.

FIGS. 16D1 through 16D5 illustrate the signal processing operations ofthe data recovery circuit of FIG. 14 for the particular symbol sequence{1,1,x}, where x represents a don't care symbol (i.e., either a data-0symbol or a data-1 symbol). These signal processing operations recoverthe “1” bit value for the middle odd symbol of the sequence. Similarprocessing operations are performed to recover the bit values of thepreceding and subsequent even symbols.

FIG. 16D1 illustrates an ideal r_(c)(t) signal utilizing the M=2Modified-Miller-subcarrier signaling scheme that encodes the symbolsequence {1,1,x}.

FIG. 16D2 illustrates the S₀ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C1). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₀ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c0) signal as shown in FIG. 16D3.

FIG. 16D4 illustrates the S₁ reference waveform for the M=2Modified-Miller-subcarrier signaling scheme (FIG. 15C2). Samples of ther_(c)(t) signal that are received within the −T/2 to 3 T/2 processingwindow are samplewise multiplied (e.g., sign changed) by thecorresponding portion of the S₁ reference waveform for the time intervalbetween −T/2 and 3 T/2 and the results accumulated to generate theZ_(c1) signal as shown in FIG. 16D5.

Similar operations are performed on samples of the quadrature r_(s)(t)signal that are received within the −T/2 to 3 T/2 processing window.These signal processing operations (blocks 1710A and 1710B) generatecomplementary results. In other words, Z_(c0) corresponds to Z_(s1) andZ_(c1) corresponds to Z_(s0). The signal level of the accumulationresults at the end of the processing window (at 3 T/2) are mapped topositive values by squaring (or by absolute value functions) and thensummed together in pairs. The result sums are then used as input to thecomparison logic for bit level assignment, which recovers the “1” bitlevel for the middle data-1 symbol in the {1,1,x} sequence.

In order to recover the bit value of the subsequent even symbol, similarprocessing operations are performed over samples of the r_(c)(t) signaland r_(s)(t) signal that are received within the subsequent T/2 to 5 T/2processing window. The signal level of the accumulation results at theend of the processing window (at 5 T/2) are mapped to positive values bysquaring (or by absolute value functions) and then summed together inpairs. The result sums are then used as input to the comparison logicfor bit level assignment of the subsequent even symbol. In order torecover the bit value of the preceding even symbol, similar processingoperations are performed over samples of the r_(c)(t) signal andr_(s)(t) signal that are received within the preceding −5 T/2 to −T/2processing window.

FIG. 17 illustrates an analog implementation of the data recoverycircuit of FIG. 14 with like numerals designating analog-forms of thesignal processing functionality described above. Note that in the analogimplementation, the samplewise multiplication operations are carried outby analog multipliers and the accumulation operations are carried out byintegration circuitry.

FIG. 18 illustrates an alternate digital implementation for the datarecovery circuit 38 for decoding the Modified-Miller-subcarrier waveformand recovering the symbol clock timing of the Modified-Miller-subcarrierwaveform according to the invention. The data rate of theModified-Miller-subcarrier signaling can vary between 5 kbps and 320kbps. This data rate is selected by the Interrogator 12 by the length ofthe TR calibration waveform (FIG. 5A) and predetermined bits (i.e., theDR bit and the 2-bit M field) in the Query command communicated from theInterrogator 12 to the Tag 14. The implementation includesanalog-to-digital conversion circuitry (blocks 1702A″, 1702B″) thatsample the r_(c)(t) and r_(s)(t) signals preferably at more than twicethe Nyquist frequency (i.e., more than twice the data rate of theModified-Miller-subcarrier signaling, which can vary between 5 kbps and320 kbps). In the preferred embodiment, the r_(c)(t) and r_(s)(t)signals are sampled at a sampling rate that is at least eight times themaximum data rate of the Modified-Miller-subcarrier signaling (i.e.,eight times the maximum date rate of 320 kbps). Alternatively, thesampling rate can be controlled in accordance with the selected M value(i.e., 2, 4, or 8) such that it is at least eight times the data rate ofthe selected Modified-Miller-subcarrier signaling scheme. The in-phasesamples and the quadrature phase samples, which are each represented bya binary NRZ value {1, −1}, are stored in sample buffers 1704A″ and1704B″, respectively. The in-phase samples and the quadrature phasesamples are supplied to a clock recovery block 1706″ that processes thetime-sequential samples to generate a subcarrier clock signal that issubstantially synchronous to the transitions in theModified-Miller-subcarrier waveform. Thus, the subcarrier clock signalhas a rate that corresponds to the data rate of theModified-Miller-subcarrier waveform. Such clock recovery operations canbe accomplished in many different ways as described above. The symbolclock signal, which is substantially synchronous to symbol transitionsin the Modified-Miller-subcarrier waveform, is derived by up-convertingthe subcarrier clock signal by a factor (i.e., 2, 4, or 8) correspondingto the M value of the selected Modified-Miller-subcarrier signalingscheme.

The subcarrier and symbol clock signals generated by the clock recoveryblock 706″ are used in four signal processing paths that operate todecode symbols. Two of the four paths process the in-phase samples(block 1732A) while the other two paths process the quadrature phasesamples (block 1732B).

In the first path of block 1732A (blocks 1734A1, 1736A1, 1738A1,1740A1), the in-phase samples that fall within the −T/2 to T/2processing window are samplewise multiplied by an S₀ reference waveformgenerated by block 1706″. The S₀ reference waveform generated by block1706″ varies based upon the M value (e.g., 2, 4 or 8) of the selectedModified-Miller-subcarrier signaling scheme as shown in FIGS. 15C1, 15D1and 15E1. In the digital domain, the operations of block 1734A1 arecarried out by changing the sign of the in-phase samples in accordancewith the value of the corresponding part of the S₀ reference waveform asfollows:

Sample Reference Waveform Sign-adjusted Sample −1 −1  1 (Sign Flips) −11 −1 (No Change) 1 −1 −1 (Sign Flips) 1 1  1 (No Change)The results of the samplewise multiplication are accumulated. In thedigital domain, this operation is carried out by summing thesign-adjusted in-phase samples over the −T/2 to T/2 processing window.The result of the accumulation of block 1734A1 is stored in a storagecell in block 1736A1. The accumulation results written to the storagecell in the previous processing window (the time interval −3 T/2 to−T/2) are output and added to the accumulation results for the currentprocessing window (the time interval −T/2 to T/2) in block 1738A1. Thesum denoted Z_(c0) is then squared in block 1740A1. Alternatively, theabsolute value of the sum Z_(c0) may be calculated in block 1740A1.

In the second path (blocks 1734A2, 1736A2, 1738A2, 1740A2), the in-phasesamples that fall within the −T/2 to T/2 processing window aresamplewise multiplied by an S₁ reference waveform generated by block1706″. The S₁ reference waveform generated by block 1706″ varies basedupon the M value (e.g., 2, 4 or 8) of the selectedModified-Miller-subcarrier signaling scheme as shown in FIGS. 15C2, 15D2and 15E2. In the digital domain, the operations of block 1734A2 arecarried out by changing the sign of the in-phase samples in accordancewith the value of the corresponding part of the S₁ reference waveform asdescribed above. The results of the samplewise multiplication areaccumulated. In the digital domain, this operation is carried out bysumming the sign-adjusted in-phase samples over the −T/2 to T/2processing window. The result of the accumulation of block 1734A2 isstored in a storage cell in block 1736A2. The accumulation resultswritten to the storage cell in the previous processing window (the timeinterval −3 T/2 to −T/2) are output and added to the accumulationresults for the current processing window (the time interval −T/2 toT/2) in block 1738A2. The sum denoted Z_(c1) is then squared in block1740A2. Alternatively, the absolute value of the sum Z_(c1) may becalculated in block 1740A2.

In block 1732B, the operations of blocks 1734A1 to 1740A2 as describedabove are performed on corresponding quadrature samples to therebyrealize the other two processing paths.

The S₀ reference waveforms are shown in FIGS. 15C1, 15D1, and 15E1 anddescribed above in detail. The S₁ reference waveforms are shown in FIGS.15C2, 15D2, and 15E2 and described above in detail. In essence, themultiplication, accumulation and storage cell access operations carriedout in each one of the four processing paths of blocks 1732A and 1732Bare digital equivalents of a matched filter implementation over a twosymbol period (i.e., over a 2 T period) which is dictated by twosuccessive processing windows that extend from −T/2 to 3 T/2. Thesquaring function (or absolute value function) maps the accumulationresults of each respective path into positive numbers such theaccumulation results can be effectively combined. The outputs of thesquaring functions (or absolute value functions) from complementarypaths are summed together. In this manner, block 1742A sums the squaredaccumulation results (or the absolute value of such accumulated results)for the Z_(c0) processing path (blocks 1734A1, 1736A1, 1738A1, 1740A1)and the Z_(s0) processing path (not shown) in block 1732B, and block1742B sums the squared accumulation results (or the absolute value ofsuch accumulation results) for the Z_(c1) processing path (blocks1734A2, 1736A2, 1738A2, 1740A2) and the Z_(s1) processing path (notshown) in block 1732B.

The output (Z0) of adder block 1742A and the output (Z1) of adder block1742B are supplied to comparison logic 1744 that assigns a binary valueof 0 or 1 for the current symbol based thereon. Such assignment ispreferably realized by the following comparison operations:

if (Z0 > Z1), then the current symbol is assigned to binary value 0;else the current symbol is assigned to binary value 1 endif; where Z0 isthe output of the adder block 1742A and Z1 is the output of the adderblock 1742B.

Controls signals, which are synchronized to the symbol clock timing, aresupplied by the symbol clock recovery block 1706″ to multiplexer 1746such that bit value is output for the current symbol time period (0 toT). Such operations are repeated for successive processing windows. Inthis manner, the output of the multiplexer 1746 provides bit estimatesfor successive symbols in the Tag's Uplink Information Signal 40.

The bit estimates output by the multiplexer 1746 may optionally beloaded into a post-processing block (not shown) that processes theestimates to cancel interference (such as co-channel interference ormulti-path interference) as described above.

The data recovery circuitry of the Interrogator 12 as described hereinincludes functionality that is activated in particular operational modescorresponding to the Tag-to-Interrogator signaling schemes (i.e.,FM0-type signaling scheme or one of the threeModified-Miller-subcarrier-type signaling schemes) that can be selectedby the Interrogator. Preferably, the processor 16 maintains one or morestate variables that identifies the selected Tag-to-Interrogatorsignaling scheme, and activates the functionality of the data recoverycircuitry for the particular operational mode corresponding to theselected signaling scheme in conjunction with transmission of the Querycommand from the Interrogator 12 to the at least one Tag 14. Such Querycommand dictates the signaling scheme that will be used for subsequentTag-to-Interrogator communications.

FIG. 19 is a high-level functional block diagram of an RFID tag 14′according to an exemplary embodiment of the present invention. The RFIDtag 14′ is shown to include one or more antennae 51′ coupled to anintegrated circuit 1912 via an interface 1911. The integrated circuit1912 includes power rectification and regulation circuitry 1913 that iscoupled to the antennae 51′ by interface 1911. The power circuitry 1913extracts power from the RF signal received at the antennae 51′ andconverts such power to one or more appropriate DC voltage levels forsupply to the components of integrated circuit 1912.

The integrated circuit 1912 also includes a demodulator 1915 that iscoupled to the antennae 51′ by the interface 1911. The demodulator 1915demodulates the RF signal received at the antenna 51′. The demodulator1915 is capable of demodulating any one of the three modulation-types(i.e., DSB-ASK, SSB-ASK or PR-ASK) that is used for downlinkcommunication from the Interrogator 12 to the Tag 14′. The demodulatedsignal components (which carry pulse-interval-encoded waveforms) aresupplied to a downlink decoder 1917 which processes the demodulatedsignal components to recover command data and parameters encodedtherein. The command data and parameters are supplied to control logic1919, which performs a control function that transitions betweenoperational states as dictated by the command data and parameterssupplied thereto.

The control logic 1919 also interfaces to a memory 1921 thatpersistently stores information such as a tag identifier, access controldata, operational parameters and configuration data (e.g., frequencycontrol words that are supplied to the clock generator 1923 fordictating the center frequencies of channels used in Tag-to-Interrogatorsignaling), and other information. The control logic 1919 alsointerfaces to an uplink encoder 1925, which operates to encodeinformation (such as the tag identifier read from memory 1921 inresponse to a request communicated from the Interrogator 12) in anuplink signal. This uplink signal is supplied to a modulator 1927 whichoperates to vary the impedance of the antenna 51′ (thereby switching thereflection coefficient of the antenna 51′) between two states inaccordance with the uplink signal. In this manner, the antenna 51′ andthe modulator 1927 cooperate to transmit a backscatter signal that ismodulated in accordance with the uplink signal supplied to the modulator1927. Preferably, the modulator 1927 employs either amplitude shiftkeying modulation or phase shift keying modulation to carry out thebackscatter modulation operations.

The clock generator 1923 provides one or more clock signals to thedemodulator 15 suitable for demodulating the RF signal received at theantennae 51′. The control logic 1919 controls the operation of thedemodulator 1915 and the modulator 1927 by respective control paths 1916and 1928.

In accordance with the present invention, the control logic 1919maintains state information that identifies the particular signalingscheme (i.e., FM0-type signaling or one of the threeModified-Miller-subcarrier signaling schemes as described herein). Suchstate information is updated in accordance with the particular signalingscheme identified in each Query command transmitted from theInterrogator 12 to the Tag 14′. The control logic 1919 controls theuplink encoder 1925 via control path 1926 to generate the uplink signalutilizing the particular signaling scheme (either FM0-type signaling orone of the three Modified-Miller-subcarrier signaling schemes) asidentified by the state information maintained therein. As describedabove, this signaling scheme is selected by the Interrogator 12 as partof the Query command communicated from the Interrogator 12 to the Tag14′. Under control of control logic 1919 via control path 1924, theclock generator 1923 provides the uplink encoder 1925 with the necessaryclock signals for generating the waveforms of the selected signalingscheme, which preferably include a symbol clock signal for FM0-typesignaling and a subcarrier clock signal and symbol clock signal forModified-Miller-subcarrier signaling. In the preferred embodiment, thesymbol clock signal for Modified-Miller-subcarrier signaling is derivedby dividing down the subcarrier clock signal by a factor based on the Mvalue (2, 4 or 8) of the selected Modified-Miller-subcarrier signalingscheme. For FM0-type signaling, the symbol clock signal supplied by theclock generator 1923 is utilized by the uplink encoder 1925 to generateFM0 waveforms as illustrated in FIGS. 3A-3D and described above indetail. For Modified-Miller-subcarrier signaling, the symbol clocksignal supplied by the clock generator 1923 is utilized by the uplinkencoder 1925 to generate a Modified-Miller baseband waveform as shown inFIGS. 4A and 4B and described above in detail. The uplink encoder 1925generates the Modified-Miller-subcarrier waveform by multiplying theModified-Miller baseband waveform with the subcarrier clock signalgenerated by the clock generator 1923 (i.e., a square wave at M timesthe symbol rate) as depicted in FIG. 4C and described above in detail.

Advantageously, the in-phase and quadrature signal processing paths ofthe Interrogator's data recovery circuit allows for accurate decodingwhere there is phase error between the CW RF carrier transmitted by theInterrogator 12 and the received modulated CW RF carrier, whichtypically results in multipath environments. Moreover, themultiplication and integration operations over the extended processingwindow of 2 T symbol periods enhances the knowledge of the energy of thesignal as well as the noise process of the communication channel. Theseenhancements increase the signal to noise ratio of the receiversubsystem, which allows for decreased signal power at the Tag (orincreased read range of the system) in order to maintain a prescribedbit error rate. The decreased signal power at the Tag is typicallyrealized by a smaller Tag antenna, which allows for a reduction in thesize and costs of the Tag.

These enhancements result from the architecture of the data recoverycircuit as well as properties of the S₀ and S₁ reference waveforms forthe FM0-type signaling and Modified-Miller-subcarrier signaling that areused therein. More particularly, for FM0-type signaling, the S₀reference waveform (FIG. 9A) has a period of T and the S₁ referencewaveform (FIG. 10A) has a period of 2 T. Thus, the composite S₁reference waveform has a period twice that of the composite S₀ referencewaveform. For Modified-Miller-Subcarrier signaling, the S₁ referencewaveforms (FIGS. 15C2, 15D2, 15E2) are derived from a basis waveform(FIG. 15A2) having a period of T and the S₀ reference waveforms (FIGS.15C, 15D1, 15E1) are derived from a basis waveform (FIG. 15A1) having aperiod of 2 T. Thus, the S₀ basis waveform has a period twice that ofthe S₁ basis waveform. In addition, the S0 and S1 reference waveformsused for either the FM0-type signaling or theModified-Miller-subcarrier-type signaling are each orthogonal in naturein that its mean is zero over its respective period. In other words, theintegral of each reference waveform over its respective period is zero.These properties improve the performance of the receiver in multipathenvironments by canceling out errors (including phase delays andamplitude variations) that arise in such multipath environments.

Moreover, the waveforms of the FM0-type signaling and theModified-Miller-subcarrier signaling share many of the same properties.This enables the encode and decode processing for the two signalingschemes to share much of the same functionality. For software-basedimplementations, this reduces the code space required for encoding ordecoding. For hardware-based implementations, this reduces the amount ofcircuitry required for encoding or decoding. These advantages areparticularly important for encoding at the Tag where reduction in codespace or circuitry can significantly reduce the size and costs of theTag.

In alternate embodiments, the data recovery circuitry of theInterrogator as described herein can include functionality that performsdemodulation and decoding of the Miller-modulated signaling. Suchfunctionality is typically realized by a phase-lock loop architecturethat recovers the baseband Miller waveforms from the Miller-modulatedsubcarrier signal and data detection circuitry that processes thebaseband Miller waveforms to assign bit levels thereto. Any othersuitable implementation can be used as well. Similarly, the Tags of thepresent invention can also include uplink signal generation circuitrythat selectively operates in a third mode to generate the uplink signalin accordance with Miller-modulated signaling.

There have been described and illustrated herein an exemplary embodimentof an Interrogator and Tags of an RFID system and improved symboldecoding and encoding mechanisms therein. While particular embodimentsof the invention have been described, it is not intended that theinvention be limited thereto, as it is intended that the invention be asbroad in scope as the art will allow and that the specification be readlikewise. Thus, while an interrogator architecture that employs a sharedantenna for the transmitter and receiver has been disclosed, it will beappreciated that an interrogator architecture that employs separatetransmit and receive antennas coupled by a circulator can be used aswell. Also, while a particular homodyne quadrature receiver architecturehas been disclosed, it will be appreciated that other receiverarchitectures can be used as well. In addition, while particularmodulation techniques and signaling formats have been disclosed, it willbe understood that other modulation techniques and signaling formats canbe used. Also, while the embodiments of FIGS. 8, 12, 14 and 18 describedherein employ separate processing paths that perform odd symbol and evensymbol processing in parallel, it will be recognized that otheralternatives can be used. For example, it is possible to separate theodd symbol and even symbol processing into three phases. The first phaseprocesses the received signal components over the processing windowbetween −T/2 and T/2. The second phase processes the received signalcomponents over the processing window between T/2 and 3 T/2. The thirdphase processes the received signal components over the processingwindow between 3 T/2 and 5 T/2. The odd symbol processing isaccomplished by accumulating the multiplication results over the firstand second phases and adding the accumulation results of the first phaseto the accumulation results of the second phase. The even symbolprocessing is accomplished by accumulating the multiplication resultsover the second and third phases and adding the accumulation results ofthe second phase to the accumulation results of the third phase. It willalso be appreciated that the symbol decoding operations described hereincan be performed over extended processing windows that are smaller thantwo times the symbol period T (e.g., smaller than 2 T) so long as suchextended processing windows are greater than T. It will therefore beappreciated by those skilled in the art that yet other modificationscould be made to the provided invention without deviating from itsspirit and scope as claimed.

What is claimed is:
 1. In a radio frequency identification systemwherein at least one RFID tag generates an uplink message represented byan uplink signal transmitted by backscatter modulation of a radiofrequency signal, the uplink signal comprising a sequence of symbols, anInterrogator comprising: a transmitter that transmits the radiofrequency signal; and a receiver that receives, demodulates, and decodesthe backscatter-modulated radio frequency signal transmitted by the atleast RFID tag in order to recover the uplink message therein, saidreceiver including symbol decoding means that operates in one of a firstmode of operation and a second mode of operation to decode the sequenceof symbols of the uplink signal; wherein, in said first mode ofoperation, the symbol decoder generates a first set of referencewaveforms that are derived by multiplying first-type bi-phase basebandwaveforms by a square wave, wherein the first-type bi-phase basebandwaveforms each have a phase inversion at least on every symbol boundaryand each have a first symbol rate SR1, and wherein the square wave has arate M*SR1, where M is selected from a number of different integervalues, and wherein, in said second mode of operation, the symboldecoder generates a second set of reference waveforms that comprisesecond-type bi-phase baseband waveforms each having a phase inversion atleast on every symbol boundary and each having a second symbol rate SR2,wherein said second symbol rate is different from said first symbol rateSR1.
 2. An Interrogator according to claim 1, wherein: in the first modeof operation, the uplink signal comprises a sequence of symbolstransmitted at the first symbol rate SR1, each symbol having acorresponding first symbol period SP1 dictated by the first symbol rateSR1, and the symbol decoding means decodes a given symbol by operatingon portions of a component of the modulated radio frequency signal thatare received over a first extended processing window, wherein the firstextended processing window is greater than said first symbol period SP1;and in the second mode of operation, the uplink signal comprises asequence of symbols transmitted at the second symbol rate SR2, eachsymbol having a corresponding second symbol period SP2 dictated by thesecond symbol rate SR2, and the symbol decoding means decodes a givensymbol by operating on portions of a component of the modulated radiofrequency signal that are received over a second extended processingwindow, wherein the second extended processing window is greater thansaid second symbol period SP2.
 3. An Interrogator according to claim 2,wherein: in the first mode of operation, a leading part of the firstextended processing window precedes the first symbol period SP1 for agiven symbol, a middle part of the first extended processing windowincludes the first symbol period SP1 for the given symbol, and an endpart of the first extended processing window follows the first symbolperiod SP1 for the given symbol; and in the second mode of operation, aleading part of the second extended processing window precedes thesecond symbol period SP2 for a given symbol, a middle part of the secondextended processing window includes the second symbol period SP2 for thegiven symbol, and an end part of the second extended processing windowfollows the second symbol period SP2 for the given symbol.
 4. AnInterrogator according to claim 2, wherein: in the first mode ofoperation, the first extended processing window has a time duration thatis substantially two times the first symbol period SP1; and in thesecond mode of operation, the second extended processing window has atime duration that is substantially two times the second symbol periodSP1.
 5. An Interrogator according to claim 4, wherein: in the first modeof operation, a leading part of the first extended processing windowprecedes the first symbol period SP1 for a given symbol, a middle partof the first extended processing window includes the first symbol periodSP1 for the given symbol, and an end part of the first extendedprocessing window follows the first symbol period SP1 for the givensymbol, wherein the leading and end parts of the first extendedprocessing window have time durations that are at least one half of thefirst symbol period SP1; and in the second mode of operation, a leadingpart of the second extended processing window precedes the second symbolperiod SP2 for a given symbol, a middle part of the second extendedprocessing window includes the second symbol period SP2 for the givensymbol, and an end part of the second extended processing window followsthe second symbol period SP2 for the given symbol, wherein the leadingand end parts of the second extended processing window have timedurations that are at least one half of the second symbol period SP2. 6.An Interrogator according to claim 2, wherein: said symbol decodingmeans includes first multiplication means, operating in said first modeof operation, for samplewise multiplication of portions of the componentof the modulated radio frequency signal with portions of said first setof reference waveforms; first accumulation means, operating in saidfirst mode of operation, for accumulating results of the firstmultiplication means over the first extended processing window; secondmultiplication means, operating in said second mode of operation, forsamplewise multiplication of portions of the component of the modulatedradio frequency signal with portions of said second set of referencewaveforms; and second accumulation means, operating in said second modeof operation, for accumulating results of the second multiplicationmeans over the second extended processing window.
 7. An Interrogatoraccording to claim 2, wherein: said transmitter comprises an RF signalsource that generates the radio frequency signal, and said receiverincludes a quadrature mixer for demodulating the modulated radiofrequency signal received by the receiver, said quadrature mixeroperably coupled to said RF signal source for homodyne demodulation. 8.An Interrogator according to claim 7, wherein: said receiver includeslow-pass filter circuitry that filters the output of the quadraturemixer to generate in-phase and quadrature signal components that aredemodulated from the modulated radio frequency signal received by thereceiver.
 9. An Interrogator according to claim 8, wherein: in saidfirst mode of operation, the symbol decoding means decodes a givensymbol by operating on portions of both the in-phase and quadraturesignal components that are received over said first extended processingwindow; and in said second mode of operation, the symbol decoding meansdecodes a given symbol by operating on portions of both the in-phase andquadrature signal components that are received over said second extendedprocessing window.
 10. An Interrogator according to claim 9, wherein: inthe first mode of operation, said symbol decoding means includes ii)first multiplication means for samplewise multiplication of portions ofthe in-phase component of the modulated radio frequency signal withportions of a reference waveform RW1 belonging to said first set ofreference waveforms, first accumulation means for accumulating resultsof the first multiplication means over the first extended processingwindow, and first squaring means for squaring output of the firstaccumulation means; iii) second multiplication means for samplewisemultiplication of portions of the quadrature component of the modulatedradio frequency signal with portions of the reference waveform RW1,second accumulation means for accumulating results of the secondmultiplication means over the first extended processing window, andsecond squaring means for squaring output of the second accumulationmeans; iv) third multiplication means for samplewise multiplication ofportions of the in-phase component of the modulated radio frequencysignal with portions of a reference waveform RW2 belonging to said firstset of reference waveforms, third accumulation means for accumulatingresults of the third multiplication means over the first extendedprocessing window, and third squaring means for squaring output of thethird accumulation means; v) fourth multiplication means for samplewisemultiplication of portions of the quadrature component of the modulatedradio frequency signal with portions of the reference waveform RW2,fourth accumulation means for accumulating results of the fourthmultiplication means over the first extended processing window, andfourth squaring means for squaring output of the fourth accumulationmeans; vi) first summing means for summing contributions of the firstand second squaring means; vii) second summing means for summingcontributions of the third and fourth squaring means; and viii)comparison logic for assigning bit values to the given symbol based uponoutput of the first and second summing means.
 11. An Interrogatoraccording to claim 10, wherein: in the second mode of operation, saidsymbol decoding means includes ii) fifth multiplication means forsamplewise multiplication of portions of the in-phase component of themodulated radio frequency signal with portions of a reference waveformRW3 belonging to said second set of reference waveforms, fifthaccumulation means for accumulating results of the fifth multiplicationmeans over the second extended processing window, and fifth squaringmeans for squaring output of the fifth accumulation means; iii) sixthmultiplication means for samplewise multiplication of portions of thequadrature component of the modulated radio frequency signal withportions of the reference waveform RW3, sixth accumulation means foraccumulating results of the sixth multiplication means over the secondextended processing window, and sixth squaring means for squaring outputof the sixth accumulation means; iv) seventh multiplication means forsamplewise multiplication of portions of the in-phase component of themodulated radio frequency signal with portions of a reference waveformRW4 belonging to said second set of reference waveforms, seventhaccumulation means for accumulating results of the seventhmultiplication means over the second extended processing window, andseventh squaring means for squaring output of the seventh accumulationmeans; v) eighth multiplication means for samplewise multiplication ofportions of the quadrature component of the modulated radio frequencysignal with portions of the reference waveform RW4, eighth accumulationmeans for accumulating results of the eighth multiplication means overthe second extended processing window, and eighth squaring means forsquaring output of the eighth accumulation means; vi) third summingmeans for summing contributions of the fifth and sixth squaring means;vii) fourth summing means for summing contributions of the seventh andeighth squaring means; and viii) comparison logic for assigning bitvalues to the given symbol based upon output of the third and fourthsumming means.
 12. An Interrogator according to claim 11, wherein: thefirst squaring means is substituted by first means for deriving absolutevalue of the accumulation results of the first accumulation means; thesecond squaring means is substituted by second means for derivingabsolute value of the accumulation results of the second accumulationmeans; the third squaring means is substituted by third means forderiving absolute value of the accumulation results of the thirdaccumulation means; and the fourth squaring means is substituted byfourth means for deriving absolute value of the accumulation results ofthe fourth accumulation means, the fifth squaring means is substitutedby fifth means for deriving absolute value of the accumulation resultsof the fifth accumulation means; the sixth squaring means is substitutedby sixth means for deriving absolute value of the accumulation resultsof the sixth accumulation means; the seventh squaring means issubstituted by seventh means for deriving absolute value of theaccumulation results of the seventh accumulation means; and the eighthsquaring means is substituted by eighth means for deriving absolutevalue of the accumulation results of the eighth accumulation means. 13.An Interrogator according to claim 11, wherein: the first, second,third, fourth, fifth, sixth, seventh and eighth accumulation means eachemploy a storage cell.
 14. An Interrogator according to claim 9,wherein: said symbol decoder employs multiple signal processing pathsfor carrying out odd symbol processing in parallel with even symbolprocessing.
 15. An Interrogator according to claim 1, wherein: themodulated radio frequency signal transmitted by the at least one RFIDtag employs one of amplitude shift keying modulation and phase shiftkeying modulation.
 16. An Interrogator according to claim 1, wherein: inthe first mode of operation, the first symbol rate SR1 varies between 5kbps and 320 kbps as dictated by downlink communication from theInterrogator to the at least one RFID tag; and in the second mode ofoperation, the second symbol rate SR2 varies between 40 kbps and 640kbps as dictated by downlink communication from the Interrogator to theat least one RFID tag.
 17. An Interrogator according to claim 16,wherein: in the first mode of operation, the first symbol rate SR1 isdictated by the length of a predetermined calibration waveformcommunicated from the Interrogator to the at least one RFID tag; and inthe second mode of operation, the second symbol rate SR2 is dictated bythe length of a predetermined calibration waveform communicated from theInterrogator to the at least one RFID tag.
 18. An Interrogator accordingto claim 2, wherein: said first-type bi-phase baseband waveforms includea first waveform with a period 2 times the first symbol period SP1 and asecond waveform with a period corresponding to the first symbol periodSP1; and said second-type bi-phase baseband waveforms include a thirdwaveform with a period corresponding to the second symbol period SP2 anda fourth waveform with a period 2 times the second symbol period SP2.19. An Interrogator according to claim 2, wherein: each first-typebi-phase baseband waveform is orthogonal in manner that its mean over aperiod 2 times the first symbol period SP1 is zero; and each second-typebi-phase baseband waveform is orthogonal in manner that its mean over aperiod 2 times the second symbol period SP2 is zero.
 20. In a radiofrequency identification system wherein at least one tag modulates aradio frequency signal by modulated backscatter operations, wherein themodulated radio frequency signal transmitted by the at least one tagencodes an uplink message that is represented by a sequence of symbols,a method for receiving the modulated radio frequency signal comprising:receiving the modulated radio frequency signal at an antenna; amplifyingcomponents of the received modulated radio frequency signal;demodulating the amplified components of received modulated radiofrequency signal; decoding a given symbol by selectively operating inone of a first operational mode and a second operation mode, wherein, insaid first mode of operation, the decoding generates a first set ofreference waveforms that are derived by multiplying first-type bi-phasebaseband waveforms by a square wave, wherein the first-type bi-phasebaseband waveforms each have a phase inversion at least on every symbolboundary and each have a first symbol rate SR1, and wherein the squarewave has a rate M*SR1, where M is selected from a number of differentinteger values, and wherein, in said second mode of operation, thedecoding generates a second set of reference waveforms that comprisesecond-type bi-phase baseband waveforms each having a phase inversion atleast on every symbol boundary and each having a second symbol rate SR2,wherein said second symbol rate is different from said first symbol rateSR1.
 21. A method according to claim 20, wherein: in the first mode ofoperation, the uplink signal comprises a sequence of symbols transmittedat the first symbol rate SR1, each symbol having a corresponding firstsymbol period SP1 dictated by the first symbol rate SR1, and thedecoding decodes a given symbol by operating on portions of a componentof the modulated radio frequency signal that are received over a firstextended processing window, wherein the first extended processing windowis greater than said first symbol period SP1; and in the second mode ofoperation, the uplink signal comprises a sequence of symbols transmittedat the second symbol rate SR2, each symbol having a corresponding secondsymbol period SP2 dictated by the second symbol rate SR2, and thedecoding decodes a given symbol by operating on portions of a componentof the modulated radio frequency signal that are received over a secondextended processing window, wherein the second extended processingwindow is greater than said second symbol period SP2.
 22. A methodaccording to claim 21, wherein: in the first mode of operation, aleading part of the first extended processing window precedes the firstsymbol period SP1 for a given symbol, a middle part of the firstextended processing window includes the first symbol period SP1 for thegiven symbol, and an end part of the first extended processing windowfollows the first symbol period SP1 for the given symbol; and in thesecond mode of operation, a leading part of the second extendedprocessing window precedes the second symbol period SP2 for a givensymbol, a middle part of the second extended processing window includesthe second symbol period SP2 for the given symbol, and an end part ofthe second extended processing window follows the second symbol periodSP2 for the given symbol.
 23. A method according to claim 21, wherein:in the first mode of operation, the first extended processing window hasa time duration that is substantially two times the first symbol periodSP1; and in the second mode of operation, the second extended processingwindow has a time duration that is substantially two times the secondsymbol period SP1.
 24. A method according to claim 23, wherein: in thefirst mode of operation, a leading part of the first extended processingwindow precedes the first symbol period SP1 for a given symbol, a middlepart of the first extended processing window includes the first symbolperiod SP1 for the given symbol, and an end part of the first extendedprocessing window follows the first symbol period SP1 for the givensymbol, wherein the leading and end parts of the first extendedprocessing window have time durations that are at least one half of thefirst symbol period SP1; and in the second mode of operation, a leadingpart of the second extended processing window precedes the second symbolperiod SP2 for a given symbol, a middle part of the second extendedprocessing window includes the second symbol period SP2 for the givensymbol, and an end part of the second extended processing window followsthe second symbol period SP2 for the given symbol, wherein the leadingand end parts of the second extended processing window have timedurations that are at least one half of the second symbol period SP2.25. A method according to claim 21, wherein: in the first mode ofoperation, the decoding includes samplewise multiplication of portionsof the component of the modulated radio frequency signal with portionsof said first set of reference waveforms, and accumulating results ofthe samplewise multiplication over the first extended processing window;and in the second mode of operation, the decoding includes samplewisemultiplication of portions of the component of the modulated radiofrequency signal with portions of said second set of referencewaveforms, and accumulating results of the samplewise multiplicationover the second extended processing window.
 26. A method according toclaim 25, wherein: the demodulation is carried out by a quadrature mixerthat generates in-phase and quadrature signal components and low-passfilter circuitry that filters the output of the quadrature mixer.
 27. Amethod according to claim 26, wherein: in said first mode of operation,the decoding decodes a given symbol by operating on portions of both thein-phase and quadrature signal components that are received over saidfirst extended processing window; and in said second mode of operation,the decoding decodes a given symbol by operating on portions of both thein-phase and quadrature signal components that are received over saidsecond extended processing window.
 28. A method according to claim 27,wherein: in said first mode of operation, the decoding includes i)samplewise multiplication of portions of the in-phase component of themodulated radio frequency signal with portions of a reference waveformRW1 belonging to said first set of reference waveforms to obtain firstmultiplication results, accumulating the first multiplication resultsover the first extended processing window to obtain a first accumulationresult, squaring of the first accumulation result to obtain a firstresultant value, ii) samplewise multiplication of portions of thequadrature phase component of the modulated radio frequency signal withportions of the reference waveform RW1 belonging to said first set ofreference waveforms to obtain second multiplication results,accumulating the second multiplication results over the first extendedprocessing window to obtain a second accumulation result, and squaringof the second accumulation result to obtain a second resulting value,iii) samplewise multiplication of portions of the in-phase component ofthe modulated radio frequency signal with portions of a referencewaveform RW2 belonging to said first set of reference waveforms toobtain third multiplication results, accumulating the thirdmultiplication results over the first extended processing window toobtain a third accumulation result, squaring of the third accumulationresult to obtain a third resultant value, iv) samplewise multiplicationof portions of the quadrature phase component of the modulated radiofrequency signal with portions of the reference waveform RW2 belongingto said first set of reference waveforms to obtain fourth multiplicationresults, accumulating the fourth multiplication results over the firstextended processing window to obtain a fourth accumulation result, andsquaring of the fourth accumulation result to obtain a fourth resultingvalue, v) summing together the first and second resultant values toobtain a first sum, vi) summing together the third and fourth resultantvalues to obtain a second sum, and vii) assigning bit values to thegiven symbol based upon the first and second sums, and in said secondmode of operation, the decoding includes viii) samplewise multiplicationof portions of the in-phase component of the modulated radio frequencysignal with portions of a reference waveform RW3 belonging to saidsecond set of reference waveforms to obtain fifth multiplicationresults, accumulating the fifth multiplication results over the secondextended processing window to obtain a fifth accumulation result,squaring of the fifth accumulation result to obtain a fifth resultantvalue, ix) samplewise multiplication of portions of the quadrature phasecomponent of the modulated radio frequency signal with portions of thereference waveform RW3 belonging to said second set of referencewaveforms to obtain sixth multiplication results, accumulating the sixthmultiplication results over the second extended processing window toobtain a sixth accumulation result, and squaring of the sixthaccumulation result to obtain a sixth resulting value, x) samplewisemultiplication of portions of the in-phase component of the modulatedradio frequency signal with portions of a reference waveform RW4belonging to said second set of reference waveforms to obtain seventhmultiplication results, accumulating the seventh multiplication resultsover the second extended processing window to obtain a seventhaccumulation result, squaring of the seventh accumulation result toobtain a seventh resultant value, xi) samplewise multiplication ofportions of the quadrature phase component of the modulated radiofrequency signal with portions of the reference waveform RW4 belongingto said second set of reference waveforms to obtain eighthmultiplication results, accumulating the eighth multiplication resultsover the second extended processing window to obtain an eighthaccumulation result, and squaring of the eighth accumulation result toobtain an eighth resulting value, xii) summing together the fifth andsixth resultant values to obtain a third sum, xiii) summing together theseventh and eighth resultant values to obtain a fourth sum, and xiv)assigning bit values to the given symbol based upon the third and fourthsums.
 29. A method according to claim 28, wherein: the symbol decodingemploys multiple signal processing paths for carrying out odd symbolprocessing in parallel with even symbol processing.
 30. A methodaccording to claim 28, wherein: the squaring operations are substitutedby absolute value determinations.
 31. A method according to claim 28,wherein: the accumulating operations employ storage cells.
 32. A methodaccording to claim 20, wherein: the modulated radio frequency signalemploys one of amplitude shift keying modulation and phase shift keyingmodulation.
 33. A method according to claim 20, wherein: in the firstmode of operation, the first symbol rate SR1 varies between 5 kbps and320 kbps as dictated by downlink communication to the at least one tag;and in the second mode of operation, the second symbol rate SR2 variesbetween 40 kbps and 640 kbps as dictated by downlink communication tothe at least one tag.
 34. A method according to claim 33, wherein: inthe first mode of operation, the first symbol rate SR1 is dictated bythe length of a predetermined calibration waveform communicated to theat least one tag; and in the second mode of operation, the second symbolrate SR2 is dictated by the length of a predetermined calibrationwaveform communicated to the at least one tag.
 35. A method according toclaim 21, wherein: said first-type bi-phase baseband waveforms include afirst waveform with a period 2 times the first symbol period SP1 and asecond waveform with a period corresponding to the first symbol periodSP1; and said second-type bi-phase baseband waveforms include a thirdwaveform with a period corresponding to the second symbol period SP2 anda fourth waveform with a period 2 times the second symbol period SP2.36. A method according to claim 21, wherein: each first-type bi-phasebaseband waveform is orthogonal in manner that its mean over a period 2times the first symbol period SP1 is zero; and each second-type bi-phasebaseband waveform is orthogonal in manner that its mean over a period 2times the second symbol period SP2 is zero.